Preamble symbol receiving method and device

ABSTRACT

Provided are a preamble symbol receiving method and device, characterizing in that the method comprises the following steps: processing a received signal; judging whether the processed signal obtained contains the preamble symbol desired to be received; and if a judgement result is yes, determining the position of the preamble symbol and resolving signalling information carried by the preamble symbol, wherein the received preamble symbol comprises at least one time-domain symbol generated by a transmitting end using a free combination of any number of first three-segment structures and/or second three-segment structures according to a predefined generation rule, the first three-segment structure containing: a time-domain main body signal, a prefix generated based on the entirety or a portion of the time-domain main body signal, and a postfix generated based on the entirety or a portion of a partial time-domain main body signal, and the second three-segment structure containing: the time-domain main body signal, a prefix generated based on the entirety or a portion of the time-domain main body signal, and a hyper prefix generated based on the entirety or a portion of the partial time-domain main body signal.

TECHNICAL FIELD

The present invention relates to the technical field of communications,and especially to a preamble symbol receiving method and device.

BACKGROUND ART

Typically, in order to enable a receiving end of an OFDM system tocorrectly demodulate data sent by a transmitting end, the OFDM systemhas to realize accurate and reliable time synchronization between thetransmitting end and the receiving end. At the same time, since the OFDMsystem is very sensitive to the frequency offset of a carrier, thereceiving end of the OFDM system also has to adopt an accurate andefficient carrier frequency estimation method, so as to preciselyestimate and correct the carrier frequency offset.

At present, a signal of an OFDM system is composed of physical frames,and each physical frame generally has one synchronization frame headreferred to as a preamble symbol or bootstrap, for realizing the timeand frequency synchronization between a transmitting end and a receivingend. The preamble symbol is known to both the transmitting end and thereceiving end, and is generally referred to as a P1 symbol. The usage ofthe P1 symbol or bootstrap symbol includes:

1) Enabling the receiving end to make a detection rapidly to determinewhether a signal transmitted in a channel is a signal desired to bereceived; 2) providing a basic transmission parameter (e.g. the numberof FFT points, frame type information, etc.), so that the receiving endcan perform subsequent receiving processing; 3) detecting initialcarrier frequency offset and a timing error, and compensating same toachieve frequency and timing synchronization; and 4) emergency alarm orbroadcast system wakeup.

A P1 symbol design based on an existing time-domain structure isproposed in existing standards such as DVB_T2 standard, which wellachieves the above-mentioned functions. However, there are still somelimitations on low-complexity receiving algorithms. By way of example,in the case of long and multi-path channels with 1024, 542, or 482samples, rough timing synchronization will cause great deviation, thusleading mistake when estimating integral frequency offset of the carrierin the frequency domain. Further, in a complex frequency selectivefading channel, for example in a long multi-path channel, DBPSKdifferential decoding method may also fail. Moreover, since thetime-domain structure of the preamble symbol in the DVB_T2 standard doesnot include a cyclic prefix, when channel estimation needs to beconducted by utilizing the preamble symbol, the frequency-domain channelestimation performance thereof will be severely degraded.

SUMMARY OF THE INVENTION

The problem to be solved by the present invention is that at present, inDVB_T2 standard and other standards, the time-domain structure of thepreamble symbol in the DVB_T2 standard cannot be applied to coherentdetection, in a complex frequency selective fading channel, the DBPSKdifferential decoding method of the preamble symbol would fail, and thereceiving algorithm detection will probably fail.

In order to solve the problem, the embodiments of the present inventionprovide the following preamble symbol receiving method and device.

Method I

The embodiments of the present invention provide a preamble symbolreceiving method, characterizing by comprising the following steps:processing a received signal; judging whether the processed signalobtained contains the preamble symbol desired to be received; and if ajudgement result is yes, determining the position of the preamble symboland resolving signalling information carried by the preamble symbol,wherein the received preamble symbol comprises at least one time-domainsymbol generated by a sending end using a free combination of any numberof first three-segment structures and/or second three-segment structuresaccording to a predefined generation rule, the first three-segmentstructure containing: a time-domain main body signal, a prefix generatedbased on the entirety or a portion of the time-domain main body signal,and a postfix generated based on the entirety or a portion of a partialtime-domain main body signal, and the second three-segment structurecontaining: the time-domain main body signal, a prefix generated basedon the entirety or a portion of the time-domain main body signal, and ahyper prefix generated based on the entirety or a portion of the partialtime-domain main body signal.

Optionally, the provided preamble symbol receiving method furthercomprise such features: the steps of judging whether the processedsignal obtained contains the preamble symbol desired to be received, andif a judgement result is yes, determining the position of the preamblesymbol and resolving signalling information carried by the preamblesymbol contain at least any one of the following steps: initial timingsynchronization, integer frequency offset estimation, fine timingsynchronization, channel estimation, decoding analysis and fractionalfrequency offset estimation.

Optionally, the provided preamble symbol receiving method furthercomprise such features: at least any one of the following is utilized tojudge if the processed signal contains the preamble symbol desired to bereceived: an initial timing synchronization method, an integer frequencyoffset estimation method, a fine timing synchronization method, achannel estimation method, a decoding result analysis method and afractional frequency offset estimation method.

Optionally, the provided preamble symbol receiving method furthercomprise such features: the position of the preamble symbol ispreliminarily determined by means of initial timing synchronization, andit is judged, based on a result of the initial timing synchronization,whether the processed signal contains the preamble symbol containing thethree-segment structure and desired to be received.

Optionally, the provided preamble symbol receiving method furthercomprise such features: the position of the preamble symbol ispreliminarily determined by means of any one of the following initialtiming synchronization methods, a first initial timing synchronizationmethod, comprising: performing necessary inverse processing on thereceived signal, which has been processed, by utilizing an associationrelationship between any two segments in a first predefinedthree-segment time-domain structure and/or a second predefinedthree-segment time-domain structure, and performing delayed movingautocorrelation to acquire basic accumulation correlation values; whenthe signal comprises at least two time-domain symbols with athree-segment structure, grouping the basic accumulation correlationvalues according to different delay lengths of the delayed movingautocorrelation, and performing at least one delay relationship matchand/or phase adjustment between symbols in each group according to aspecific assembling relationship of the at least two time-domainsymbols, and then carrying out a mathematical calculation to obtainseveral final accumulation correlation values with regard to a certaindelay length, and when there is only one time-domain symbol with athree-segment structure, the final accumulation correlation value is thebasic accumulation correlation value; and after performing delayrelationship match and/or a specific predefined mathematical calculationbased on at least one of the final accumulation correlation values,using the result of the calculation for initial timing synchronization;a second initial timing synchronization method, comprising: when atime-domain main body signal in any three-segment structure in thepreamble symbol contains a known signal, performing a differentialoperation on the time-domain main body signal in accordance with Npredefined differential values, and also performing a differentialoperation on a time-domain signal corresponding to known information,then correlating the two to obtain N sets of differential correlatedresults corresponding to the N differential values on a one-to-onebasis, and performing initial synchronization based on the N sets ofdifferential correlated results to obtain processed values forpreliminarily determining the position of the preamble symbol, whereN≧1, wherein when the determination of the position of the preamblesymbol is accomplished based on the first initial timing synchronizationmethod and the second initial timing synchronization method, weightingthe processed values obtained respectively, and completing initialtiming synchronization using the weighted results.

Optionally, the provided preamble symbol receiving method furthercomprise such features: the first initial timing synchronization methodcomprises: when the signal comprises two time-domain symbols withthree-segment structure, grouping the basic accumulation correlationvalues according to different delay lengths of the delayed movingautocorrelation, and for each set, performing one delay relationshipmatch and/or phase adjustment between symbols according to a assemblingrelationship specific to the two time-domain symbols, and then carryingout a mathematical calculation to obtain several final accumulationcorrelation values with regard to a certain delay length.

Optionally, the provided preamble symbol receiving method furthercomprise such features: the first initial timing synchronization methodfurther comprises adjusting, within a certain range, delay lengths thatthere should be during each delayed moving autocorrelation, to form aplurality of adjusted delay lengths; then performing delayed movingautocorrelation according to the plurality of obtained adjusted delaylengths and the delay lengths that there should be, and choosing acorrelation result which is the most significant as the basicaccumulation correlation value.

Optionally, the provided preamble symbol receiving method furthercomprise such features: the N differential values are selected accordingto at least any one of the following predefined differential selectionrules, for initial synchronization: a first predefined differentialselection rule containing: selecting any several differential valueswithin the range of the length of a local time-domain sequencecorresponding to the know information; and a second predefineddifferential selection rule containing: selecting several differentialvalues which constitute an arithmetic sequence, within the range of thelength of the local time-domain sequence corresponding to the knowinformation.

Optionally, the provided preamble symbol receiving method furthercomprise such features: when the N differential values are selectedusing the first predefined differential selection rule, accumulating oraveraging the weighted absolute values of N sets of differentialcorrelated results obtained on a one-to-one basis; or when the Ndifferential values are selected using the first predefined differentialselection rule or the second predefined differential selection rule,accumulating or averaging weighted vectors of the obtained N sets ofdifferential correlated results.

Optionally, the provided preamble symbol receiving method furthercomprise such features: fractional frequency offset estimation isconducted by utilizing a result of the first initial timingsynchronization method and/or the second initial timing synchronizationmethod, when a result of the first initial timing synchronization methodis used, the result comprises the final accumulation correlation valueobtained by performing predefined processing calculation utilizing aprocessing relationship corresponding to the time-domain main bodysignal and the prefix in the first three-segment structure and/or thesecond three-segment structure, and a second fractional frequency offsetvalue is calculated from the accumulation correlation value; the resultof the first initial timing synchronization method also comprises twosaid final accumulation correlation values obtained by performingpredefined processing calculation utilizing a processing relationshipcorresponding to the time-domain main body signal and the postfix/thehyper prefix and a processing relationship corresponding to the prefixand the postfix/the hyper prefix in the first three-segment structureand/or the second three-segment structure, and a third fractionalfrequency offset value is calculated from the two accumulationcorrelation values; the fractional frequency offset estimation can beconducted based on at least any one of the obtained second fractionalfrequency offset value and third fractional frequency offset value; andwhen utilizing the results of the first initial timing synchronizationmethod and the second initial timing synchronization method, afractional frequency offset value is obtained based on at least any oneof or a combination of at least any two of the first fractionalfrequency offset value, the second fractional frequency offset value andthe third fractional frequency offset value.

Optionally, the provided preamble symbol receiving method furthercomprise such features: based on a result of the initial timingsynchronization method, if it is detected that the result satisfies apre-set condition, then it is determined that the processed signalcontains an expected preamble symbol containing the three-segmentstructure, wherein the pre-set condition contains: conducting a specificcalculation based on the result of the initial timing synchronization,and then judging whether the maximum value of a calculation resultexceeds a predefined threshold, or further determining it in conjunctionwith an integer frequency offset estimation result and/or a decodingresult.

Optionally, the provided preamble symbol receiving method furthercomprise such features: the preamble symbol receiving method furthercomprises: conducting fractional frequency offset estimation byutilizing a result of an initial timing synchronization method.

Optionally, the provided preamble symbol receiving method furthercomprise such features: the step of determining the position of thepreamble symbol and resolving signalling information carried by thepreamble symbol comprises: resolving the signalling information carriedby the preamble symbol by utilizing the entirety or a portion of atime-domain waveform of the preamble symbol and/or a frequency-domainsignal obtained through performing Fourier transform on the time-domainwaveform.

Optionally, the provided preamble symbol receiving method furthercomprise such features: in the predefined generation rule, the generatedpreamble symbol comprises: a free combination of several time-domainsymbols with the first three-segment structure and/or severaltime-domain symbols with the second three-segment structure arranged inany order. the first three-segment structure containing: a time-domainmain body signal, a prefix generated based on a rear part of thetime-domain main body signal, and a postfix generated based on the rearpart of the time-domain main body signal, and the second three-segmentstructure containing: a time-domain main body signal, a prefix generatedbased on a rear part of the time-domain main body signal, and a hyperprefix generated based on the rear part of the time-domain main bodysignal.

Optionally, the provided preamble symbol receiving method furthercomprise such features: when a transmitting end generates the postfix orthe hyper prefix by truncating the time-domain main body signal to get apartial signal, different start points of the truncation are used fortransmitting different signalling information, and the signalling isparsed based on the following: different delay relationships of the samecontent between the prefix and the postfix or the hyper prefix, and/orthe time-domain main body signal and the postfix or the hyper prefix.

Optionally, the provided preamble symbol receiving method furthercomprise such features: the parsed signalling contains emergencybroadcast.

Optionally, the provided preamble symbol receiving method furthercomprise such features: the preamble symbol is obtained by processing afrequency-domain symbol, and the generation step of the frequency-domainsymbol comprises: arranging a fixed sequence and a signalling sequence,which are generated respectively, in a predefined arrangement rule, andfilling valid subcarriers with arranged fixed sequence and signallingsequence.

Optionally, the provided preamble symbol receiving method furthercomprise such features: the step of resolving signalling informationcarried by the preamble symbol comprises: resolving the signallinginformation carried by signalling sequence subcarriers in the preamblesymbol by performing calculation using a signal containing all or someof the signalling sequence subcarriers and a set of signalling sequencesubcarriers, or resolving the signalling information carried by thesignalling sequence subcarriers in the preamble symbol by performingcalculation using a time-domain signal corresponding to the entire or aportion of the set of signalling sequence subcarriers.

Optionally, the provided preamble symbol receiving method furthercomprise such features: conducting fine timing synchronization using afixed subcarrier sequence contained in at least one time-domain symbol.

Optionally, the provided preamble symbol receiving method furthercomprise such features: when the time-domain main body signal in thepreamble symbol or a corresponding frequency-domain main body signalcontains a known signal, the preamble symbol receiving method furthercomprises integer frequency offset estimation in any of the followingmanners: according to a result of the initial timing synchronization,truncating to get a section of time-domain signal at least containingthe entirety or a portion of the time-domain main body signal,modulating the truncated section of time-domain signal using differentfrequency offsets in a frequency sweeping manner to obtain N frequencysweeping time-domain signals corresponding to the offset values on aone-to-one basis, and after performing moving correlation between aknown time-domain signal obtained by performing inverse Fouriertransform on a known frequency-domain sequence and each frequencysweeping time-domain signal, comparing the maximum correlation peaks ofN correlation results, regarding a frequency offset value by which afrequency sweeping time-domain signal corresponding to the maximumcorrelation result is modulated as the integer frequency offsetestimation value; or performing Fourier transform on the time-domainsignal which is truncated to the length of the time-domain main bodysignal according to the result of the initial timing synchronization,conducting cyclic shift on the obtained frequency-domain subcarriersusing different shift values within a frequency sweeping range,truncating a received sequence corresponding to a valid subcarrier,performing predefined calculation and then inverse transform on thereceived sequence and the known frequency-domain sequence, performingselection from several groups of inverse transform results correspondingto the shift values on a one-to-one basis to obtain a correspondingshift value, and obtaining the integer frequency offset estimation valueaccording to a corresponding relationship between the shift value andthe integer frequency offset estimation value.

Optionally, the provided preamble symbol receiving method furthercomprise such features: the step of channel estimation comprises:performing arbitrarily on the time domain and/or on the frequencydomain: after finishing the decoding of the previous time-domain mainbody signal, using obtained decoded information as known information toperform channel estimation on the time domain/frequency domain onceagain and perform certain specific calculation on a previous channelestimation result to obtain a new channel estimation result, which willbe used in channel estimation of signalling parsing for the nexttime-domain main body signal.

Optionally, the provided preamble symbol receiving method furthercomprise such features: the received preamble symbol is obtained byprocessing the frequency-domain subcarrier, the frequency-domainsubcarrier being generated based on the frequency-domain main bodysequence, The steps of generating the frequency-domain subcarriercontains: a predefined sequence generation rule for generating thefrequency-domain main body sequence, and/or a predefined processing rulefor processing the frequency-domain main body sequence for generatingthe frequency-domain subcarrier. The predefined sequence generation rulecontains either one or a combination of two of the following: generatinga sequence based on different sequence generation formulas; and/orgenerating a sequence based on the same sequence generation formula, andfurther preforming cyclic shift on the generated sequence. Thepredefined processing rule contains: according to the frequency offsetvalue, performing phase modulation on a pre-generated subcarrier whichis obtained by processing the frequency-domain main body sequence.

Optionally, the provided preamble symbol receiving method furthercomprise such features: when the preamble symbol at least contains onetime-domain symbol, in the case where a first time-domain symbolcontains known information, fine timing synchronization is conducted byutilizing the known information.

Optionally, the provided preamble symbol receiving method furthercomprise such features: in the step of parsing signalling information,firstly, producing a set of known signalling sequences using allpossible different root values and/or different frequency-domain shiftvalues, and then conducting calculation using the set of signallingsequences and all possible frequency-domain modulation frequency offsetvalues and a frequency-domain main body sequence transmitted by thetransmitting end.

Optionally, the provided preamble symbol receiving method furthercomprise such features: when the time-domain main body signal in thepreamble symbol or a corresponding frequency-domain main body signalcontains a known signal, the preamble symbol receiving method furthercomprises integer frequency offset estimation in any of the followingmanners: according to a result of the initial timing synchronization,truncating to get a section of time-domain signal at least containingthe entirety or a portion of the time-domain main body signal,modulating the truncated section of time-domain signal using differentfrequency offsets in a frequency sweeping manner to obtain N frequencysweeping time-domain signals corresponding to the offset values on aone-to-one basis, and after performing moving correlation between aknown time-domain signal obtained by performing inverse Fouriertransform on a known frequency-domain sequence and each frequencysweeping time-domain signal, comparing the maximum correlation peaks ofN correlation results, regarding a frequency offset value by which afrequency sweeping time-domain signal corresponding to the maximumcorrelation result is modulated as the integer frequency offsetestimation value; or performing Fourier transform on the time-domainsignal which is truncated to the length of the time-domain main bodysignal according to the result of the initial timing synchronization,conducting cyclic shift on the obtained frequency-domain subcarriersusing different shift values within a frequency sweeping range,truncating a received sequence corresponding to a valid subcarrier,performing predefined calculation and then inverse transform on thereceived sequence and the known frequency-domain sequence, performingselection from several groups of inverse transform results correspondingto the shift values on a one-to-one basis to obtain a correspondingshift value, and obtaining the integer frequency offset estimation valueaccording to a corresponding relationship between the shift value andthe integer frequency offset estimation value.

Optionally, the provided preamble symbol receiving method furthercomprise such features: the step of channel estimation comprises:performing arbitrarily on the time domain and/or on the frequencydomain: after finishing the decoding of the previous time-domain mainbody signal, using obtained decoded information as known information toperform channel estimation on the time domain/frequency domain onceagain and perform certain specific calculation on a previous channelestimation result to obtain a new channel estimation result, which willbe used in channel estimation of signalling parsing for the nexttime-domain main body signal.

Optionally, the provided preamble symbol receiving method furthercomprise such features: after the integer frequency offset estimation,compensating the frequency offset and parsing the transmittedsignalling.

Optionally, the provided preamble symbol receiving method furthercomprise such features: when generating a sequence using differentsequence generation formulas; and/or generating a sequence based on thesame sequence generation formula, and further preforming cyclic shift onthe generated sequence, in the process of generating thefrequency-domain subcarrier, performing a specific mathematicalcalculation on the frequency-domain signalling subcarrier and thechannel estimation value, and all possible frequency-domain main bodysequence, so as to parse the signalling, wherein the specificmathematical calculation contains any one of the following: maximumlikelihood correlation calculation incorporating channel estimation; orperforming channel equalization on the frequency-domain signallingsubcarrier using the channel estimation value, then performingcorrelation calculation with all of the possible frequency-domain mainbody sequences, and selecting the maximum correlation value as adecoding result of signalling parsing.

Optionally, the provided preamble symbol receiving method furthercomprise such features: the process of generating the frequency-domainsubcarrier includes: performing phase modulation on a pre-generatedsubcarrier using the frequency offset value, or performing cyclic shiftin the time domain after inverse Fourier transform.

Optionally, the provided preamble symbol receiving method furthercomprise such features: the step of determining the position of thepreamble symbol and parsing signalling information carried by thepreamble symbol comprises: performing Fourier transform on thetime-domain main body signal of each of the time-domain symbol toextract valid subcarriers; performing predefined mathematicalcalculation using each of the valid subcarriers and a known subcarriercorresponding to each known frequency-domain sequence in a set of knownfrequency-domain signalling of the time-domain symbol and a channelestimation value, and then performing inverse Fourier transform, andobtaining a corresponding inverse Fourier result for each of the knownfrequency-domain sequence; and each of the time-domain symbol selectingan inverse Fourier selection result from one or more of the inverseFourier results according to a first predefined selection rule, thenperforming a predefined processing operation using a plurality of thetime-domain symbols, and resolving the signalling information based onan obtained inter-symbol processing result.

Optionally, the provided preamble symbol receiving method furthercomprise such features: calculating the absolute value or square of theabsolute value of the inverse Fourier selection result, and thenselecting the inverse Fourier selection result according to the firstpredefined selection rule.

Optionally, the provided preamble symbol receiving method furthercomprise such features: the first predefined selection rule containsperforming selection according to the maximum peak value and/orperforming selection according to the peak-to-average ratio.

Optionally, the provided preamble symbol receiving method furthercomprise such features: the method further comprises a noise filteringprocessing step comprising: noise filtering processing can be performedon the inverse Fourier result of each time-domain symbol, with largevalues being reserved and all smaller values being set to zero.

Optionally, the provided preamble symbol receiving method furthercomprise such features: the parsed signalling information contains:signalling transmitted using different frequency-domain sequences and/orsignalling transmitted using a frequency-domain modulation frequencyoffset, i.e. a time-domain cyclic shift value.

Optionally, the provided preamble symbol receiving method furthercomprise such features: the set of known frequency-domain signallingrefers to all possible frequency-domain sequences of the time-domainmain body signal corresponding to each time-domain symbol onfrequency-domain subcarrier modulation while phase modulation is notperformed.

Optionally, the provided preamble symbol receiving method furthercomprise such features: if there is only one known sequence within a setof known frequency-domain sequences of the time-domain symbols, thefirst predefined selection rule is: directly selecting the uniqueinverse Fourier result of each of the time-domain symbols as the inverseFourier selection result, then performing a predefined processingoperation between a plurality of the time-domain symbols, and resolvingthe signalling information based on an obtained inter-symbol processingresult.

Optionally, the provided preamble symbol receiving method furthercomprise such features: the predefined mathematical calculationcontains: conjugate multiplication or division calculation.

Optionally, the provided preamble symbol receiving method furthercomprise such features: the step of performing a predefined processingoperation between a plurality of the time-domain symbols and resolvingthe signalling information based on an obtained inter-symbol processingresult comprises: multiplying or conjugate multiplying a latertime-domain symbol which have been cyclically shifted and a formertime-domain symbol, and accumulating to obtain an accumulated value,finding out a shift value corresponding to a maximum accumulated valuein all the predefined frequency offset values or cyclic shift values,and deriving the signalling information from the shift value.

Optionally, the provided preamble symbol receiving method furthercomprise such features: the step of determining the position of thepreamble symbol and parsing signalling information carried by thepreamble symbol comprises: extending the set of known frequency-domainsignalling of each time-domain symbol to be an extended set of knownfrequency-domain signalling. performing Fourier transform on thetime-domain main body signal of each of the time-domain symbol toextract valid subcarriers; performing predefined mathematicalcalculation using each of the valid subcarriers and the known subcarriercorresponding to each known frequency-domain sequence in the extendedset of known frequency-domain signalling and the channel estimationvalue, and then accumulating the calculation values on all the validsubcarriers; and selecting an accumulated value from a plurality ofaccumulated values according to a second predefined selection rule,using a known frequency-domain sequence of the extended set of knownfrequency-domain signalling corresponding to the accumulated value toinfer the signalling transmitted using the frequency-domain modulationfrequency offset value, i.e. the time-domain cyclic shift, and selectinga corresponding known frequency-domain sequence from the original set ofknown frequency-domain signalling before extension, so as to resolvesignalling information transmitted by different frequency-domainsequences.

Optionally, the provided preamble symbol receiving method furthercomprise such features: the second predefined selection rule containsperforming selection according to the maximum absolute value orperforming selection according to the maximum real part.

Optionally, the provided preamble symbol receiving method furthercomprise such features: the set of known frequency-domain signallingrefers to all possible frequency-domain sequences of the time-domainmain body signal corresponding to each time-domain symbol onfrequency-domain subcarrier while phase modulation is not performed.

Optionally, the provided preamble symbol receiving method furthercomprise such features: the extended set of known frequency-domainsignalling is obtained in the following way: performing phase modulationon of each known frequency-domain sequence of the set of knownfrequency-domain signalling on the subcarriers using all possiblefrequency offset values, wherein all the possible S modulation frequencyoffset values correspondingly generate S frequency offset modulatedknown sequences.

Optionally, the provided preamble symbol receiving method furthercomprise such features: when there is only one known sequence within thenon-extended set of known frequency-domain signalling of the symbol,namely, the signalling information is transmitted only by afrequency-domain modulation frequency offset s, i.e., the time-domaincyclic shift value, the extended set of known frequency-domainsignalling contains altogether S known frequency-domain sequences, andthe modulation frequency offset value can be inferred by utilizing theknown frequency-domain sequences of the extended set of knownfrequency-domain signalling corresponding to the modulation frequencyoffset s, thus obtaining the signalling information transmitted by thefrequency-domain modulation frequency offset, i.e. the time-domaincyclic shift.

Optionally, the provided preamble symbol receiving method furthercomprise such features: the predefined mathematical calculationcontains: conjugate multiplication or division calculation.

Optionally, the provided preamble symbol receiving method furthercomprise such features: the step of determining the position of thepreamble symbol and parsing signalling information carried by thepreamble symbol comprises: performing Fourier transform on thetime-domain main body signal of each of the time-domain symbol toextract valid subcarriers; performing predefined mathematicalcalculation using each of the valid subcarriers and a known subcarriercorresponding to each known frequency-domain sequence in a set of knownfrequency-domain signalling of the time-domain symbol and a channelestimation value, and then performing inverse Fourier transform, andobtaining a corresponding inverse Fourier transform result for each ofthe known frequency-domain sequence; and each of the time-domain symbol,based on an inverse Fourier selection result selected from one or moreof the inverse Fourier results according to a first predefined selectionrule, performing a predefined processing operation using a plurality ofthe time-domain symbols, and resolving the signalling information basedon an obtained inter-symbol processing result.

Optionally, the provided preamble symbol receiving method furthercomprise such features: the method further comprises: calculating theabsolute value or square of the absolute value of the inverse Fourierselection result, and then selecting the inverse Fourier selectionresult according to the first predefined selection rule.

Optionally, the provided preamble symbol receiving method furthercomprise such features: the first predefined selection rule containsperforming selection according to the maximum peak value and/orperforming selection according to the peak-to-average ratio.

Optionally, the provided preamble symbol receiving method furthercomprise such features: the method further comprises a noise filteringprocessing step comprising: noise filtering processing can be performedon the inverse Fourier result of each time-domain symbol, with largevalues being reserved and all smaller values being set to zero.

Optionally, the provided preamble symbol receiving method furthercomprise such features: the parsed signalling information contains:signalling transmitted using different frequency-domain sequences and/orsignalling transmitted using a frequency-domain modulation frequencyoffset, i.e. a time-domain cyclic shift value.

Optionally, the provided preamble symbol receiving method furthercomprise such features: the set of known frequency-domain signallingrefers to all possible frequency-domain sequences of the time-domainmain body signal corresponding to each time-domain symbol that are usedfor filling the frequency-domain subcarriers while phase modulation isnot performed.

Optionally, the provided preamble symbol receiving method furthercomprise such features: if there is only one known sequence within a setof known frequency-domain sequences of the time-domain symbols, thefirst predefined selection rule is: directly selecting the uniqueinverse Fourier result of each of the time-domain symbols as the inverseFourier selection result, then performing a predefined processingoperation between a plurality of the time-domain symbols, and resolvingthe signalling information based on an obtained inter-symbol processingresult.

Optionally, the provided preamble symbol receiving method furthercomprise such features: the predefined mathematical calculationcontains: conjugate multiplication or division calculation.

Optionally, the provided preamble symbol receiving method furthercomprise such features: the step of performing a predefined processingoperation between a plurality of the time-domain symbols and resolvingthe signalling information based on an obtained inter-symbol processingresult comprises: multiplying or conjugate multiplying a latertime-domain symbol and a former time-domain symbol which have beencyclically shifted, and accumulating to obtain an accumulated value,finding out a shift value corresponding to a maximum accumulated valuein all the predefined frequency offset values or cyclic shift values,and deriving the signalling information from the shift value.

Method II

Furthermore, the embodiments of the present invention also provide apreamble symbol receiving method, characterizing by comprising thefollowing steps: processing a received signal; judging whether theprocessed signal obtained contains the preamble symbol desired to bereceived; and if a judgement result is yes, determining the position ofthe preamble symbol and resolving signalling information carried by thepreamble symbol, wherein the received preamble symbol is obtained byprocessing a frequency-domain symbol, and the generation step of thefrequency-domain symbol comprises: arranging a fixed sequence and asignalling sequence, which are generated respectively, in a predefinedarrangement rule, and filling valid subcarriers with the arranged fixedsequence and signalling sequence.

Optionally, the provided preamble symbol receiving method furthercomprise such features: at least any one of the following method isutilized to judge if the processed signal contains the preamble symboldesired to be received: an initial timing synchronization method, aninteger frequency offset estimation method, a fine timingsynchronization method, a channel estimation method, a decoding resultanalysis method and a fractional frequency offset estimation method.

Optionally, the provided preamble symbol receiving method furthercomprise such features: the functions of judging if the received signal,which has been processed, contains the preamble symbol desired to bereceived, and if a judgement result is yes, determining the position ofthe preamble symbol and resolving signalling information carried by thepreamble symbol contains are realized by utilizing at least any one ofthe following steps: initial timing synchronization, integer frequencyoffset estimation, fine timing synchronization, channel estimation,decoding analysis and fractional frequency offset estimation.

Optionally, the provided preamble symbol receiving method furthercomprise such features: using the fixed sequence to perform an integerfrequency offset estimation or channel estimation comprises thefollowing steps: according to the determined position of the preamblesymbol, truncating to get a signal containing the entirety or a portionof the fixed subcarrier; and performing calculation using the truncatedsignal and a frequency-domain fixed subcarrier sequence or a time-domainsignal corresponding to the frequency-domain fixed subcarrier sequence,so as to realize an integer frequency offset estimation or channelestimation.

Optionally, the provided preamble symbol receiving method furthercomprise such features: conducting fine timing synchronization using afixed subcarrier sequence contained in at least one time-domain symbolin the preamble symbol.

Optionally, the provided preamble symbol receiving method furthercomprise such features: the step of determining the position of thepreamble symbol and resolving signalling information carried by thepreamble symbol comprises: resolving the signalling information carriedby the preamble symbol by utilizing the entirety or a portion of atime-domain waveform of the preamble symbol and/or a frequency-domainsignal obtained through performing Fourier transform on the entirety ora portion of the time-domain waveform of the preamble symbol.

Optionally, the provided preamble symbol receiving method furthercomprise such features: when the time-domain main body signal in thepreamble symbol or a corresponding frequency-domain main body signalcontains a known signal, the method further comprises performing any ofthe following integer frequency offset estimation using the preamblesymbol: according to a result of the initial timing synchronization,truncating to get a section of time-domain signal at least containingthe entirety or a portion of the time-domain main body signal,modulating the truncated section of time-domain signal using differentfrequency offsets in a frequency sweeping manner to obtain N frequencysweeping time-domain signals corresponding to the offset values on aone-to-one basis, and after performing moving correlation between aknown time-domain signal obtained by performing inverse transform on aknown frequency-domain sequence and each frequency sweeping time-domainsignal, comparing the maximum correlation peaks of N correlationresults, regarding a frequency offset value by which a frequencysweeping time-domain signal corresponding to the maximum correlationresult is modulated as the integer frequency offset estimation value; orperforming Fourier transform on the time-domain signal which istruncated to the length of the time-domain main body signal using theresult of the initial timing synchronization, conducting cyclic shift onthe obtained frequency-domain subcarriers using different shift valueswithin a frequency sweeping range, truncating a received sequencecorresponding to a valid subcarrier, performing predefined calculationand then inverse Fourier transform on the received sequence and theknown frequency-domain sequence, performing selection from severalgroups of inverse transform results corresponding to the shift values ona one-to-one basis to obtain a corresponding shift value, and obtainingthe integer frequency offset estimation value according to acorresponding relationship between the shift value and the integerfrequency offset estimation value.

Optionally, the provided preamble symbol receiving method furthercomprise such features: the step of resolving signalling informationcarried by the preamble symbol comprises: resolving the signallinginformation carried by signalling sequence subcarriers in the preamblesymbol by performing calculation using a signal containing all or someof the signalling sequence subcarriers and a set of signalling sequencesubcarriers, or a time-domain signal corresponding to the set ofsignalling sequence subcarriers,

Method III

Furthermore, the embodiments of the present invention also provide apreamble symbol receiving method, characterizing by comprising thefollowing steps: processing a received signal; judging whether thereceived signal which has been processed contains the preamble symboldesired to be received; and if a judgement result is yes, determiningthe position of the preamble symbol and resolving signalling informationcarried by the preamble symbol, the received preamble symbol is obtainedby performing inverse Fourier transform on the frequency-domainsubcarrier, the frequency-domain subcarrier being generated based on thefrequency-domain main body sequence, The steps of generating thefrequency-domain subcarrier contains: a predefined sequence generationrule for generating the frequency-domain main body sequence, and/or apredefined processing rule for processing the frequency-domain main bodysequence for generating the frequency-domain subcarrier. The predefinedsequence generation rule contains either one or a combination of two ofthe following: generating a sequence based on different sequencegeneration formulas; and/or generating a sequence based on the samesequence generation formula, and further preforming cyclic shift on thegenerated sequence. The predefined processing rule contains: accordingto the frequency offset value, performing phase modulation on apre-generated subcarrier which is obtained by processing thefrequency-domain main body sequence.

Optionally, the provided preamble symbol receiving method furthercomprise such features: the steps of judging whether the processedsignal obtained contains the preamble symbol desired to be received, andif a judgement result is yes, determining the position of the preamblesymbol and resolving signalling information carried by the preamblesymbol contain at least any one of the following steps: initial timingsynchronization, integer frequency offset estimation, fine timingsynchronization, channel estimation, decoding analysis and fractionalfrequency offset estimation.

Optionally, the provided preamble symbol receiving method furthercomprise such features: at least any one of the following method isutilized to judge if the processed signal contains the preamble symboldesired to be received: an initial timing synchronization method, aninteger frequency offset estimation method, a fine timingsynchronization method, a channel estimation method, a decoding resultanalysis method and a fractional frequency offset estimation method.

Optionally, the provided preamble symbol receiving method furthercomprise such features: when the preamble symbol contains at least onetime-domain symbol, if a first time-domain symbol contains knowninformation, fine timing synchronization is conducted by utilizing theknown information.

Optionally, the provided preamble symbol receiving method furthercomprise such features: the step of channel estimation comprises:performing arbitrarily on the time domain and/or on the frequencydomain: after finishing the decoding of the previous time-domain mainbody signal, using obtained decoded information as sending informationto perform channel estimation on the time domain/frequency domain onceagain and perform certain specific calculation on a previous channelestimation result to obtain a new channel estimation result, which willbe used in channel estimation of signalling parsing for the nexttime-domain main body signal.

Optionally, the provided preamble symbol receiving method furthercomprise such features: when the time-domain main body signal in thepreamble symbol or a corresponding frequency-domain main body signalcontains a known signal, the preamble symbol receiving method furthercomprises integer frequency offset estimation in any of the followingmanners: modulating the entirety or a portion of the truncatedtime-domain signal using different frequency offsets in a frequencysweeping manner to obtain several frequency sweeping time-domainsignals, and after performing moving correlation between a knowntime-domain signal obtained by performing inverse transform on a knownfrequency-domain sequence and each frequency sweeping time-domainsignal, regarding a frequency offset value by which a frequency sweepingtime-domain signal of the maximum correlation peak value is modulated asthe integer frequency offset estimation value; or conducting cyclicshift on frequency-domain subcarriers, which are obtained by performingFourier transform on the time-domain main body signal truncatedaccording to the position result of the initial timing synchronization,using different shift values within a frequency sweeping range,truncating a received sequence corresponding to valid subcarriers,performing predefined calculation and then inverse transform on thereceived sequence and the known frequency-domain sequence, obtaining ashift value from inverse transform results corresponding to severalgroups of shift values, thereby obtaining the integer frequency offsetestimation value according to a corresponding relationship between theshift value and the integer frequency offset estimation value.

Optionally, the provided preamble symbol receiving method furthercomprise such features: after the integer frequency offset estimation,compensating the frequency offset and parsing the transmittedsignalling.

Optionally, the provided preamble symbol receiving method furthercomprise such features: when generating a sequence using differentsequence generation formulas; and/or generating a sequence based on thesame sequence generation formula, and further preforming cyclic shift onthe generated sequence, in the process of generating thefrequency-domain subcarrier, a specific mathematical calculation isperformed on the frequency-domain signalling subcarrier and the channelestimation value, and all possible frequency-domain main body sequence,so as to realize signalling parsing, wherein the specific mathematicalcalculation containing any one of the following: maximum likelihoodcorrelation calculation incorporating channel estimation; or performingchannel equalization on the frequency-domain signalling subcarrier usingthe channel estimation value, then performing correlation calculationusing an equalized signal and all of the possible frequency-domain mainbody sequences, and selecting the maximum correlation value as adecoding result of signalling parsing.

Optionally, the provided preamble symbol receiving method furthercomprise such features: the step of determining the position of thepreamble symbol and resolving signalling information carried by thepreamble symbol comprises: resolving the signalling information carriedby the preamble symbol by utilizing the entirety or a portion of atime-domain waveform of the preamble symbol and/or utilizing afrequency-domain signal obtained through performing Fourier transform onthe entirety or a portion of the time-domain waveform of the preamblesymbol.

Optionally, the provided preamble symbol receiving method furthercomprise such features: the generation process of the frequency-domainsubcarrier includes: performing phase modulation on a pre-generatedsubcarrier using the predefined frequency offset value or performinginverse Fourier transform on the frequency-domain subcarriers and thenperforming cyclic shift in the time domain.

Optionally, the provided preamble symbol receiving method furthercomprise such features: the step of determining the position of thepreamble symbol and parsing signalling information carried by thepreamble symbol comprises: performing Fourier transform on thetime-domain main body signal of each of the time-domain symbol toextract valid subcarriers; performing predefined mathematicalcalculation using each of the valid subcarriers and a known subcarriercorresponding to each known frequency-domain sequence in a set of knownfrequency-domain signalling of the time-domain symbol and a channelestimation value, and then performing inverse Fourier transform, andobtaining a corresponding inverse Fourier transform result for each ofthe known frequency-domain sequence; and each of the time-domain symbol,based on an inverse Fourier selection result selected from one or moreof the inverse Fourier results according to a first predefined selectionrule, performing a predefined processing operation on a plurality of thetime-domain symbols, and resolving the signalling information based onan obtained inter-symbol processing result.

Optionally, the provided preamble symbol receiving method furthercomprise such features: the method further comprises: calculating theabsolute value or square of the absolute value of the inverse Fourierselection result, and then selecting the inverse Fourier selectionresult according to the first predefined selection rule.

Optionally, the provided preamble symbol receiving method furthercomprise such features: the first predefined selection rule containsperforming selection according to the maximum peak value and/orperforming selection according to the peak-to-average ratio.

Optionally, the provided preamble symbol receiving method furthercomprise such features: the method further comprises a noise filteringprocessing step comprising: noise filtering processing can be performedon the inverse Fourier result of each time-domain symbol, with largevalues being reserved and all smaller values being set to zero.

Optionally, the provided preamble symbol receiving method furthercomprise such features: the parsed signalling information contains:signalling transmitted using different frequency-domain sequences and/orsignalling transmitted using a frequency-domain modulation frequencyoffset, i.e. a time-domain cyclic shift value.

Optionally, the provided preamble symbol receiving method furthercomprise such features: the set of known frequency-domain signallingrefers to all possible frequency-domain sequences of the time-domainmain body signal corresponding to each time-domain symbol that are usedfor filling the frequency-domain subcarriers while phase modulation isnot performed.

Optionally, the provided preamble symbol receiving method furthercomprise such features: if there is only one known sequence within a setof known frequency-domain sequences of the time-domain symbols, thefirst predefined selection rule is: directly selecting the uniqueinverse Fourier result of each of the time-domain symbols as the inverseFourier selection result, then performing a predefined processingoperation between a plurality of the time-domain symbols, and resolvingthe signalling information based on an obtained inter-symbol processingresult.

Optionally, the provided preamble symbol receiving method furthercomprise such features: the predefined mathematical calculationcontains: conjugate multiplication or division calculation.

Optionally, the provided preamble symbol receiving method furthercomprise such features: the step of performing a predefined processingoperation between a plurality of the time-domain symbols and resolvingthe signalling information based on an obtained inter-symbol processingresult comprises: multiplying or conjugate multiplying a latertime-domain symbol which have been cyclically shifted and a formertime-domain symbol, and accumulating to obtain an accumulated value,finding out a shift value corresponding to a maximum accumulated valuein all the predefined frequency offset values or cyclic shift values,and deriving the signalling information from the shift value.

Optionally, the provided preamble symbol receiving method furthercomprise such features: the step of determining the position of thepreamble symbol and parsing signalling information carried by thepreamble symbol comprises: extending the set of known frequency-domainsignalling of each time-domain symbol to be an extended set of knownfrequency-domain signalling. performing Fourier transform of thetime-domain main body signal of each of the time-domain symbol toextract valid subcarriers; performing predefined mathematicalcalculation using each of the valid subcarriers and the known subcarriercorresponding to each known frequency-domain sequence in the extendedset of known frequency-domain signalling and the channel estimationvalue, and then accumulating the calculation values on all the validsubcarriers; and selecting an accumulated value from a plurality ofaccumulated values according to a second predefined selection rule,using a known frequency-domain sequence of the extended set of knownfrequency-domain signalling corresponding to the accumulated value toinfer the signalling which is transmitted by utilizing thefrequency-domain modulation frequency offset value, i.e. the time-domaincyclic shift, and inferring a corresponding known frequency-domainsequence in the original set of known frequency-domain signalling beforeextension, so as to resolve signalling information transmitted by adifferent frequency-domain sequence.

Optionally, the provided preamble symbol receiving method furthercomprise such features: the second predefined selection rule containsperforming selection according to the maximum absolute value orperforming selection according to the maximum real part.

Optionally, the provided preamble symbol receiving method furthercomprise such features: the set of known frequency-domain signallingrefers to all possible modulated phase frequency-domain sequences of thetime-domain main body signal corresponding to each time-domain symbolthat are used for filling the frequency-domain subcarriers while phasemodulation is not performed.

Optionally, the provided preamble symbol receiving method furthercomprise such features: the extended set of known frequency-domainsignalling is obtained in the following way: modulating the subcarrierphase of each known frequency-domain sequence of the set of knownfrequency-domain signalling correspondingly using all possible frequencyoffset values, wherein all the possible S modulation frequency offsetvalues will generate S frequency offset modulated known sequences.

Optionally, the provided preamble symbol receiving method furthercomprise such features: when there is only one known sequence within thenon-extended set of known frequency-domain signalling of the symbol,namely, the signalling information is transmitted only by afrequency-domain modulation frequency offset s, i.e., the time-domaincyclic shift value, the extended set of known frequency-domainsignalling contains altogether S known frequency-domain sequences, andthe modulation frequency offset value can be inferred by utilizing theknown frequency-domain sequences of the extended set of knownfrequency-domain signalling corresponding to the modulation frequencyoffset s, thus obtaining the signalling information transmitted by thefrequency-domain modulation frequency offset, i.e. the time-domaincyclic shift.

Optionally, the provided preamble symbol receiving method furthercomprise such features: the predefined mathematical calculationcontains: conjugate multiplication or division calculation.

Optionally, the provided preamble symbol receiving method furthercomprise such features: the step of determining the position of thepreamble symbol and parsing signalling information carried by thepreamble symbol comprises: performing Fourier transform on thetime-domain main body signal of each of the time-domain symbol toextract valid subcarriers; performing predefined mathematicalcalculation using each of the valid subcarriers and a known subcarriercorresponding to each known frequency-domain sequence in a set of knownfrequency-domain signalling of the time-domain symbol and a channelestimation value, and then performing inverse Fourier transform, andobtaining a corresponding inverse Fourier result for each of the knownfrequency-domain sequence; and each of the time-domain symbol, based onan inverse Fourier selection result selected from one or more of theinverse Fourier results according to a first predefined selection rule,performing a predefined processing operation on a plurality of thetime-domain symbols, and resolving the signalling information based onan obtained inter-symbol processing result.

Optionally, the provided preamble symbol receiving method furthercomprise such features: the predefined sending rule contains: afterprocessing a frequency-domain main body sequence corresponding to atime-domain main body signal in each transmitted time-domain signal toobtain pre-generated subcarriers, performing phase modulation on eachvalid subcarrier using a predefined frequency offset value S in thefrequency domain or performing cyclic shift in the time domain afterinverse Fourier transform.

Optionally, the provided preamble symbol receiving method furthercomprise such features: the method further comprises: calculating theabsolute value or square of the absolute value of the inverse Fourierselection result, and then selecting the inverse Fourier selectionresult according to the first predefined selection rule.

Optionally, the provided preamble symbol receiving method furthercomprise such features: the first predefined selection rule containsperforming selection according to the maximum peak value and/orperforming selection according to the peak-to-average ratio.

Optionally, the provided preamble symbol receiving method furthercomprise such features: the method further comprises a noise filteringprocessing step comprising: noise filtering processing can be performedon the inverse Fourier result of each time-domain symbol, with largevalues being reserved and all smaller values being set to zero.

Optionally, the provided preamble symbol receiving method furthercomprise such features: the parsed signalling information contains:signalling transmitted using different frequency-domain sequences and/orsignalling transmitted using frequency-domain modulation frequencyoffset, i.e. a time-domain cyclic shift value.

Optionally, the provided preamble symbol receiving method furthercomprise such features: the set of known frequency-domain signallingrefers to all possible sequences of the time-domain main body signalcorresponding to each time-domain symbol that are used for filling thefrequency-domain subcarriers before performing phase modulation on ofthe frequency-domain subcarriers.

Optionally, the provided preamble symbol receiving method furthercomprise such features: if there is only one known sequence within a setof known frequency-domain sequences of the time-domain symbols, thefirst predefined selection rule is: directly selecting the uniqueinverse Fourier result of each of the time-domain symbols as the inverseFourier selection result, then performing a predefined processingoperation between a plurality of the time-domain symbols, and resolvingthe signalling information based on an obtained inter-symbol processingresult.

Optionally, the provided preamble symbol receiving method furthercomprise such features: the predefined mathematical calculationcontains: conjugate multiplication or division calculation.

Optionally, the provided preamble symbol receiving method furthercomprise such features: the step of performing a predefined processingoperation between a plurality of the time-domain symbols and resolvingthe signalling information based on an obtained inter-symbol processingresult comprises: multiplying or conjugate multiplying a latertime-domain symbol which have been cyclically shifted and a formertime-domain symbol, and accumulating to obtain an accumulated value,finding out a shift value corresponding to a maximum accumulated valuein all the predefined frequency offset values or cyclic shift values,and deriving the signalling information from the shift value.

Device I

Additionally, the embodiments of the present invention also provide apreamble symbol receiving device, characterized by comprising: areceiving and processing unit for processing a received signal; ajudgement unit for judging whether the processed signal obtainedcontains the preamble symbol desired to be received; and a positionlocating unit for, if a judgement result is yes, determining theposition of the preamble symbol and resolving signalling informationcarried by the preamble symbol, wherein the preamble symbol received bythe receiving and processing unit comprises at least one time-domainsymbol generated by a transmitting end using a free combination of anynumber of first three-segment structures and/or second three-segmentstructures according to a predefined generation rule, the firstthree-segment structure containing: a time-domain main body signal, aprefix generated based on the entirety or a portion of the time-domainmain body signal, and a postfix generated based on the entirety or aportion of a partial time-domain main body signal, and the secondthree-segment structure containing: the time-domain main body signal, aprefix generated based on the entirety or a portion of the time-domainmain body signal, and a hyper prefix generated based on the entirety ora portion of the partial time-domain main body signal.

Device II

Additionally, the embodiments of the present invention also provide apreamble symbol receiving device, characterized by comprising: areceiving and processing unit for processing a received signal; ajudgement unit for judging whether the processed signal obtainedcontains the preamble symbol desired to be received; and a positionlocating unit for, if a judgement result is yes, determining theposition of the preamble symbol and resolving signalling informationcarried by the preamble symbol, wherein the preamble symbol received bythe receiving and processing unit is obtained by processing afrequency-domain symbol, and the generation step of the frequency-domainsymbol comprises: arranging a fixed sequence and a signalling sequence,which are generated respectively, in a predefined arrangement rule, andfilling valid subcarriers with the same.

Device III

Additionally, the embodiments of the present invention also provide apreamble symbol receiving device, characterized by comprising: areceiving unit for processing a received signal; a judgement unit forjudging whether the received signal, which has been processed, containsthe preamble symbol desired to be received; and a position locating unitfor, if a judgement result is yes, determining the position of thepreamble symbol and resolving signalling information carried by thepreamble symbol, wherein the preamble symbol received by the receivingunit is obtained by performing inverse Fourier transform on thefrequency-domain subcarrier, the frequency-domain subcarrier beinggenerated based on the frequency-domain main body sequence, The steps ofgenerating the frequency-domain subcarrier contains: a predefinedsequence generation rule for generating the frequency-domain main bodysequence, and/or a predefined processing rule for processing thefrequency-domain main body sequence for generating the frequency-domainsubcarrier. The predefined sequence generation rule contains either oneor a combination of two of the following: generating a sequence based ondifferent sequence generation formulas; and/or generating a sequencebased on the same sequence generation formula, and further preformingcyclic shift on the generated sequence. The predefined processing rulecontains: according to the frequency offset value, performing phasemodulation on a pre-generated subcarrier which is obtained by processingthe frequency-domain main body sequence.

The preamble symbol can include, but is not limited to, time-domainsymbols with one or two three-segment structures.

Compared with the prior art, the technical solutions of the presentinvention have the following beneficial effects:

according to the preamble symbol receiving method and device provided inthe embodiments of the present invention, when a time-domain main bodysignal is an OFDM symbol, the entirety or a portion of the time-domainmain body signal is used as a prefix, and coherent detection can berealized by utilizing the generated prefix, which solves the issues ofperformance degradation with non-coherent detection and differentialdecoding failure under complex frequency selective fading channels(DBPSK); and using the entirety or a portion of the time-domain mainbody signal as a postfix or hyper prefix and making optional modulationwould enable the generated preamble symbol to have sound fractionalfrequency offset estimation performance and timing synchronizationperformance.

Further, it can be chosen to transmit a time-domain symbol with athree-segment structure as a preamble symbol according to therequirements of transmission efficiency and robustness. When thepreamble symbol contains at least one symbol with a three-segmentstructure, based on the same OFDM symbol main body, a different startpoint when truncating to get the second part from the first part can beused for transmitting signalling, such as emergency broadcast, hookinformation, transmitter sign information or other transmissionparameters. By designing two different three-segment structures,emergency broadcast is identified. When the preamble symbol is generatedby using two symbols with a three-segment structure, two OFDM symbolmain bodies thereof are different, and the three-segment structuresadopted therein are also different; on this basis, emergency broadcastis identified according to the sequential order of the two three-segmentstructures. By using different three-segment structures of two symbols,the problem of fractional frequency offset estimation failure occurringin some special-length multi-path channels can be avoided.

Furthermore, using three-segment structure with partial identicalcontents (as a preamble symbol) ensures that significant peaks can beobtained by means of delayed moving auto-correlation at a receiving end.Moreover, in the process of generating the preamble symbol, a signalobtained by modulating a time-domain main body signal can avoid thefollowing: continuous wave interference or single-frequencyinterference, or the occurrence of a multi-path channel with the samelength to that of the modulated signal, on the occurrence of an errorpeak detection when the length of a guard interval in the receivedsignal is the same as that of the modulated signal.

BRIEF DESCRIPTION OF THE DRAWINGS

FIG. 1 is a schematic diagram of a time-domain symbol with a firstthree-segment structure in the embodiments of the present invention;

FIG. 2 is a schematic diagram of a time-domain symbol with a secondthree-segment structure in the embodiments of the present invention;

FIG. 3 is a schematic diagram of acquisition processing based on atime-domain symbol with the first three-segment structure in theembodiments of the present invention;

FIG. 4 is a schematic diagram of acquisition processing based on atime-domain symbol with the second three-segment structure in theembodiments of the present invention;

FIG. 5 is the structural diagram of the first three-segment structureand the second three-segment structure assembled in a first assemblingmode in the embodiments of the present invention;

FIG. 6 is the structural diagram of the first three-segment structureand the second three-segment structure assembled in a second assemblingmode in the embodiments of the present invention;

FIG. 7 is a schematic diagram of acquisition processing based on thefirst assembling mode in the embodiments of the present invention;

FIG. 8 is a schematic diagram of acquisition processing based on thesecond assembling mode in the embodiments of the present invention;

FIG. 9 is a schematic diagram of frequency-domain structure I arrangedaccording to a first predetermined interlaced arrangement rule in theembodiments of the present invention;

FIG. 10 is a schematic diagram of frequency-domain structure I arrangedaccording to a second predetermined interlaced arrangement rule in theembodiments of the present invention;

FIG. 11 is a schematic diagram of overall shift with a first shift valueaccording to a third predefined association rule in the embodiments ofthe present invention;

FIG. 12 is a schematic diagram of overall shift with a second shiftvalue according to a third predefined association rule in theembodiments of the present invention;

FIG. 13 is a schematic diagram of the arrangement of frequency-domainstructure II corresponding to a time-domain symbol in the embodiments ofthe present invention;

FIG. 14 is a logic diagram of a correlation result to be detectedcorresponding to a three-segment structure CAB in a preamble symbolreceiving method in the embodiments of the present invention;

FIG. 15 is a logic diagram of a correlation result to be detectedcorresponding to a three-segment structure BCA in a preamble symbolreceiving method in the embodiments of the present invention;

FIG. 16 a block diagram of the logic calculation for acquiring aninitial timing synchronization result to be detected using C−A−B−B−C−Asplicing mode in the embodiments of the present inventions;

FIG. 17 a block diagram of the logic calculation for acquiring aninitial timing synchronization result to be detected using B−C−A−C−A−Bsplicing mode in the embodiments of the present inventions;

FIG. 18 a block diagram of the logic calculation for acquiring aninitial timing synchronization result using 4 accumulation correlationvalues of 4 time-domain symbols in the embodiments of the presentinventions;

FIG. 19 a block diagram of the logic calculation for acquiring aninitial timing synchronization result using 2 accumulation correlationvalues of 2 time-domain symbols in the embodiments of the presentinventions;

FIG. 20 is an oscillograph of an inverse Fourier result of a time-domainmain body signal under AWGN in the embodiments of the present invention;

FIG. 21 provides an oscillograph of an inverse Fourier result of atime-domain main body signal under an 0 dB two-path channel in theembodiments;

FIG. 22(a) is an oscillograph of an inverse Fourier result of thetime-domain main body signal of the previous time-domain symbol beforenoise filter processing under an 0 dB two-path channel in theembodiments;

FIG. 22(b) is respectively an oscillograph of an inverse Fourier resultof the time-domain main body signal of the latter time-domain symbolbefore noise filter processing under an 0 dB two-path channel in theembodiments;

FIG. 23(a) is an oscillograph of an inverse Fourier result of atime-domain main body signal of the previous time-domain symbol afternoise filter processing under an 0 dB two-path channel in theembodiments;

FIG. 23(b) is respectively an oscillograph of an inverse Fourier resultof the time-domain main body signal of the latter time-domain symbolafter noise filter processing under an 0 dB two-path channel in theembodiments; and

FIG. 24 is an oscillograph of an inverse Fourier result of a time-domainmain body signal under AWGN in example II of signalling parsing of thepresent invention.

DETAILED DESCRIPTION OF THE DRAWINGS

{Generation Method}

This embodiment provides a preamble symbol generation method. Thepreamble symbol generation method comprises the following steps:generating time-domain symbols which have the following three-segmentstructures based on a time-domain main body signal; and generating thepreamble symbol based on at least one of the time-domain symbols,

FIG. 1 is a schematic diagram of a time-domain symbol with a firstthree-segment structure in the embodiments of the present invention.FIG. 2 is a schematic diagram of a time-domain symbol with a secondthree-segment structure in the embodiments of the present invention.

The generated preamble symbol comprises:

a time-domain symbol with a first three-segment structure; or

a time-domain symbol with a second three-segment structure; or

a free combination of several time-domain symbols with the firstthree-segment structure and/or several time-domain symbols with thesecond three-segment structure arranged in any order.

The following description is made to a time-domain structure of thetime-domain symbols contained in the above-mentioned preamble symbolthrough FIG. 1 and FIG. 2. The time-domain structure contains athree-segment structure; and the three-segment have two alternatives,i.e. a first three-segment structure and a second three-segmentstructure.

As shown in FIG. 1, the first three-segment structure is: a time-domainmain body signal (part A), a prefix (part C) generated by utilizing to apartial time-domain main body signal which is truncated from thetime-domain main body signal, and a modulated signal, i.e. a postfix(part B), which is generated by utilizing a portion or the entirety ofthe partial time-domain main body signal.

As shown in FIG. 2, the second three-segment structure is: a time-domainmain body signal (part A), a prefix (part C) generated by utilizing to apartial time-domain main body signal which is truncated from thetime-domain main body signal, and a modulation signal, i.e. a hyperprefix (part B), which is generated by utilizing the partial time-domainmain body signal.

Specifically, a section of a time-domain main body signal (indicated byA in the figure) is taken as a first part, a first portion is taken fromthe end of the first part according to a predefined acquisition rule,and is processed according to a first predefined processing rule andreplicated to the front of the first part to produce a third part(indicated by C in the figure), thus taking it as a prefix; at the sametime, a portion is taken from the rear of the first part according to apredefined acquisition rule, and is processed according to a secondpredefined processing rule and replicated to the rear of the first partor processed and replicated to the front of the prefix to produce asecond part (indicated by B in the figure), thus respectively taking itas a postfix or a hyper prefix correspondingly, thereby respectivelyproducing the first three-segment structure with B as the postfix asshown in FIG. 1 (CAB structure) and the second three-segment structurewith B as the hyper prefix as shown in FIG. 2 (BCA structure).

With regard to the particular rules for processing the third part andthe second part from the first part, the first predefined processingrule comprises: direct copy, or multiplying each sampling signal in thetaken part by a fixed coefficient or a predefined variable coefficient.The second predefined processing rule comprises: conducting modulationwhen the first predefined processing rule is direct copy, or when thefirst predefined processing rule is multiplying each sampling signal inthe taken part by a fixed coefficient or predefined variablecoefficient, multiplying a corresponding part by the correspondingcoefficient as well and then conducting modulation processing. That is,when the third part is directly copied as the prefix, modulationprocessing is performed on the second part as the postfix or hyperprefix by a corresponding main body part; and when the third part ismultiplied by a corresponding coefficient, the second part also needs tobe multiplied by a coefficient for modulation processing, and is thentaken as the postfix or hyper prefix.

FIG. 3 is a schematic diagram of a predefined processing rule for atime-domain symbol with a first three-segment structure in theembodiments of the present invention.

In this embodiment, section C is directly copied from section A, andsection B is a modulated signal section of section A. As shown in FIG.3, for example, the length of A is 1024, the length of C truncated is520, and the length of B is 504, wherein when processing C and B, eachsample of the signal can be multiplied with a fixed coefficient, or eachsample is multiplied by a different coefficient.

The data length of B does not exceed the data length of C, which meansthat the range in A which is selected for generating the modulatedsignal section B would not exceed the range of A truncated as the prefixC. Preferably, the sum of the length of B and that of C is the length ofA.

Let N_(A) denotes the length of A, Len_(C) denotes the length of C, andLen_(B) denotes the length of the modulation signal section B. Let thesampling point serial numbers of A be 0,1, . . . N_(A)−1. Let the firstsampling point serial number for generating the modulated signal sectionpart B in A be N1, and the final sampling point serial number forgenerating the modulated signal section part B in A be N2. The firstsampling point serial number and the second sampling point serial numbersatisfy the following predefined restriction relationship:

N2=N1+Len_(B)−1   (Formula 1)

Generally, modulation made on the second part B section is frequencyoffset modulation, i.e. multiplying a frequency shift sequence, amodulation (M) sequence or other sequences, etc. The modulationfrequency offset is taken as an example in this embodiment, assumingthat P1_A(t) is the time-domain expression of A, then the time-domainexpression of the first C−A−B three-segment structure is

           (Formula  2) ${P_{C - A - B}(t)} = \left\{ \begin{matrix}{P\; 1{\_ A}\left( {t + {\left( {N_{A} - {Len}_{C}} \right)T}} \right)} & {0 \leq t < {{Len}_{C}T}} \\{P\; 1{\_ A}\left( {t - {{Len}_{C}T}} \right)} & {{{Len}_{C}T} \leq t < {\left( {N_{A} + {Len}_{C}} \right)T}} \\{P\; 1{\_ A}\left( {t - {\begin{pmatrix}{{Len}_{C} +} \\{N_{A} -} \\{N\; 1}\end{pmatrix}T}} \right)e^{j\; 2\pi \; f_{SH}t}} & {{\left( {N_{A} + {Len}_{C}} \right)T} \leq t < {\begin{pmatrix}{N_{A} +} \\{{Len}_{C} +} \\{Len}_{B}\end{pmatrix}T}} \\0 & {otherwise}\end{matrix} \right.$

where if the time-domain main body signal is an OFDM symbol, themodulation frequency offset value f^(SH) of the frequency shift sequencecan be selected as a frequency-domain subcarrier interval i.e. 1/N_(A)Tcorresponding to a time-domain OFDM main-body signal, with T being thesampling period, N_(A) being the length of the time-domain OFDMmain-body signal. In this example, N_(A) is 1024, and f_(SH)=1/1024T.The primary phase of the frequency shift sequence may be an arbitraryvalue; and in order to enable a correlation peak to be sharp, f_(SH) canalso be selected as 1/(Len_(B)T).

As shown in FIG. 3, N_(A)1024; Len_(C)=520, Len_(B)=504, and N1=520. Atthis moment, the auto-correlation delay of section CA containing thesame content is N_(A), the auto-correlation delay of section CBcontaining the same content is N_(A)+Len_(B), and the auto-correlationdelay of section AB containing the same content is Len_(B).

In another embodiment, the length of section C is the same as that ofsection B, that is to say, section B can be considered as a completelyfrequency offset adjustment of section C.

Particularly, the cyclic prefix C is assembled at the front of thetime-domain OFDM symbol A as a guard interval, and the modulation signalsection B is assembled at the rear of the OFDM symbol as a modulationfrequency offset sequence, so as to generate a time-domain symbol withthe first three-segment structure. For example, when N_(A)=1024, theparticular expression can be as follows,

           (Formula  3) ${P_{C - A - B}(t)} = \left\{ \begin{matrix}{P\; 1{\_ A}\left( {t + {\left( {1024 - {Len}_{C}} \right)T}} \right)} & {0 \leq t < {{Len}_{C}T}} \\{P\; 1{\_ A}\left( {t - {{Len}_{C}T}} \right)} & {{{Len}_{C}T} \leq t < {\left( {1024 + {Len}_{C}} \right)T}} \\{P\; 1{\_ A}\left( {t - {2{Len}_{C}T}} \right)e^{j\; 2\pi \; f_{SH}t}} & {{\left( {1024 + {Len}_{C}} \right)T} \leq t < {\left( {1024 + {2{Len}_{C}}} \right)T}} \\0 & {otherwise}\end{matrix} \right.$

FIG. 4 is a schematic diagram of the processing of a time-domain symbolwith a second three-segment structure in the embodiments of the presentinvention.

In a similar way, the time-domain expression of the time-domain symbolwith the second three-segment structure is as follows. No that in orderto enable the processing method of the receiving end as consistent aspossible, in B−C−A structure, the modulation frequency offset value isexactly opposite to C−A−B structure, and the primary phase of themodulation frequency offset sequence can be an arbitrary value.

           (Formula  4) ${P_{B - C - A}(t)} = \left\{ \begin{matrix}{P\; 1{\_ A}\left( {t + {\left( {N\; 1} \right)T}} \right)e^{{- j}\; 2\pi \; {f_{SH}{({t - {{Len}_{C}T}})}}}} & {0 \leq t < {{Len}_{B}T}} \\{P\; 1{\_ A}\left( {t - {\begin{pmatrix}{{Len}_{B} -} \\{N_{A} +} \\{Len}_{C}\end{pmatrix}T}} \right)} & {{{Len}_{B}T} \leq t < {\left( {{Len}_{B} + {Len}_{C}} \right)T}} \\{P\; 1{\_ A}\left( {t - {\left( {{Len}_{B} + {Len}_{C}} \right)T}} \right)} & {{\left( {{Len}_{B} + {Len}_{C}} \right)T} \leq t < {\begin{pmatrix}{{Len}_{B} +} \\{{Len}_{C} +} \\N_{A}\end{pmatrix}T}} \\0 & {otherwise}\end{matrix} \right.$

As shown in FIG. 4, N_(A)=1024; Len_(C)=520, Len_(B)=504, and N1=504. Atthis moment, the auto-correlation delay of section CA containing thesame content is N_(A), the auto-correlation delay of section BCcontaining the same content is Len_(B), and the auto-correlation delayof section BA containing the same content is N_(A)+Len_(B).

Further, when the preamble symbol contains a symbol with a three-segmentstructure, no matter the three-segment structure is the firstthree-segment structure or the second three-segment structure, based onthe same OFDM symbol main body, signalling can also be transmitted usinga time-domain structure in the following way.

A different start point to select the second part from the first partcan be used for transmitting signalling, such as emergency broadcast,hook information, transmitter sign information or other transmissionparameters.

By way of example, for the first three-segment structure, for example,the predefined length is 1024, Len_(C) is 512, and Len_(B) is 256.

N1 can be valued at 512+i*16 0≦i<16, which can then indicate 16different mode to take by the second part, and transmit 4 bits ofsignalling parameters. Different transmitters can transmit an identifiercorresponding to the transmitter by taking different N1, the sametransmitter can also transmit a parameter by changing N1 in atime-division manner.

For another example, 1 bit of signalling is used for transmittingemergency broadcast identifier EAS_flag.

if EAS_flag=1, then N1=512−L, that is, taking sampling points fromserial numbers 512−L to 1023-2L of OFDM symbol with N_(A) being 1024 andperform modulation by the frequency offset sequence to generate B, andplacing it at the rear of A.

if EAS_flag=0, then N1=512+L, that is, taking sampling points fromserial numbers 512+L to 1023 of OFDM symbol with N_(A) being 1024 andperform modulation by the frequency offset sequence to generate B, andplacing it at the rear of A.

The value of L is 8.

Particularly, N_(A)=1024, Len_(C) is 520, Len_(B) is 504; N1=520indicates that EAS_flag=0, and N1=504 indicates that EAS_flag=1; orN1=504 indicates that EAS_flag=0, and N1=520 indicates that EAS_flag=1.

For another example, N_(A)=2048, Len_(C) is 520, Len_(B) is 504; N1=1544indicates that EAS_flag=0, and N1=1528 indicates that EAS_flag=1; orN1=1528 indicates that EAS_flag=0, and N1=1544 indicates thatEAS_flag=1.

Besides truncating to get the second part from the first part atdifferent start points to indicate emergency broadcast, when thepreamble symbol contains only one three-segment structure, a variablethree-segment structure can be used to identify emergency broadcast. Forexample, EAS_flag=0 can be indicated by transmitting the firstthree-segment structure C−A−B, and EAS_flag=1 is indicated bytransmitting the second three-segment structure B−C−A; alternatively,EAS_flag=1 is indicated by transmitting the first three-segmentstructure C−A−B, and EAS_flag=0 is indicated by transmitting the secondthree-segment structure B−C−A.

Besides containing a time-domain symbol with a three-segment structure,the preamble symbol can also contain the assembling of two time-domainswith a three-segment structure. When the three-segment structures of thetwo time-domain symbols are the same, the two three-segment symbols aredirectly spiced; and for two different three-segment structure, thereare two assembling ways according to the sequential order. Assemblingtwo different three-segment structures has the following advantages: insome multi-path environment with a special delay, the rear part ofsegment A of the former path may just be counteracted by segment C ofthe later path identical to A, leading to a reduction in timingsynchronization performance, and more seriously, not being able toperform small offset estimation. At this time, when assembling with twodifferent three-segment structure, even in the case of a dangerousmultipath, small offset can still be normally estimated.

In this embodiment, the preamble symbol contains a free combination ofmultiple time-domain symbols with the first three-segment structureand/or multiple time-domain symbols with the second three-segmentstructure arranged in any order. Two three-segment structure are takenas an example for explanation in this embodiment below, and the twothree-segment structures are respectively the first three-segmentstructure and the second three-segment structure.

FIG. 5 is a schematic diagram of a first method to splice twothree-segment structures in this embodiment. FIG. 6 is a schematicdiagram of a second method to splice two three-segment structures inthis embodiment.

In the time-domain symbol shown in FIG. 5 and the time-domain symbolshown in FIG. 6, respectively, the two time-domain main body signalstherein are different, and the three-segment structures adopted therebyare also different; and the first assembling method as shown in FIG. 5and the second assembling method as shown in FIG. 6 are respectivelyformed by different sequential orders of the two time-domain symbols.

No matter which assembling method is used, the time-domain main bodysignals (i.e. A) of the two time-domain symbols in FIG. 5 and FIG. 6 canbe different; in this way, the capacity for signalling transmissionafter assembling the two symbols is twice or nearly twice of that of asingle time-domain symbol with a three-segment structure. Respectivetime-domain main body symbols of at least one time-domain symbolscontained in the preamble symbol may be different and may be the same,on which there is no restriction.

A peak is acquired by means of the delayed auto-correlation of sectionCB, section CA and section BA when detecting a single time-domain symbolwith a three-segment structure; when assembling two time-domain symbolswith a three-segment structure, in order to be able to perform additionof the auto-correlation values of the two time-domain symbols with athree-segment structure and obtain more robust performance, theparameter N1 of each of the two time-domain symbols with a three-segmentstructure (that is, N1 is the sampling point serial number in Acorresponding to the start point chosen to be replicated for modulationsignal segment B) should satisfy a certain relationship, assuming thatN1 of the first symbol is N1_1, and N1 of the second symbol is N1_2,then they should satisfy N1_1+N1_2=2N_(A)−(Len_(B)+Len_(c)). Moreover,if the modulation performed on segment B is frequency offset modulation,the frequency offset value is exactly contrary.

Serial number 1 is used to indicate the symbol with the C−A−B structure,and serial number 2 is used to indicate the symbol with the B−C−Astructure. Assuming that P1_A(t) is the time-domain expression of A1,and P2_A(t) is the time-domain expression of A2, then the time-domainexpression of a time-domain symbol with the first three-segmentstructure is:

           (Formula  5) ${P_{C - A - B}(t)} = \left\{ \begin{matrix}{P\; 1{\_ A}\left( {t + {\left( {N_{A} - {Len}_{C}} \right)T}} \right)} & {0 \leq t < {{Len}_{C}T}} \\{P\; 1{\_ A}\left( {t - {{Len}_{C}T}} \right)} & {{{Len}_{C}T} \leq t < {\left( {N_{A} + {Len}_{C}} \right)T}} \\{P\; 1{\_ A}\left( {t - {\begin{pmatrix}{{Len}_{C} +} \\{N_{A} -} \\{N\; 1\_ 1}\end{pmatrix}T}} \right)e^{j\; 2\pi \; f_{SH}t}} & {{\left( {N_{A} + {Len}_{C}} \right)T} \leq t < {\begin{pmatrix}{N_{A} +} \\{{Len}_{C} +} \\{Len}_{B}\end{pmatrix}T}} \\0 & {otherwise}\end{matrix} \right.$

and then the time-domain expression of a time-domain symbol with thesecond three-segment structure is:

           (Formula  6) ${P_{B - C - A}(t)} = \left\{ \begin{matrix}{P\; 2{\_ A}\left( {t + {\left( {N\; 1\_ 2} \right)T}} \right)e^{{- j}\; 2\pi \; {f_{SH}{({t - {{Len}_{C}T}})}}}} & {0 \leq t < {{Len}_{B}T}} \\{P\; 2{\_ A}\left( {t - {\begin{pmatrix}{{Len}_{B} -} \\{N_{A} +} \\{Len}_{C}\end{pmatrix}T}} \right)} & {{{Len}_{B}T} \leq t < {\left( {{Len}_{B} + {Len}_{C}} \right)T}} \\{P\; 2{\_ A}\left( {t - {\left( {{Len}_{B} + {Len}_{C}} \right)T}} \right)} & {{\left( {{Len}_{B} + {Len}_{C}} \right)T} \leq t < {\begin{pmatrix}{{Len}_{B} +} \\{{Len}_{C} +} \\N_{A}\end{pmatrix}T}} \\0 & {otherwise}\end{matrix} \right.$

Then, as shown in FIG. 5, the time-domain expression of the time-domainsymbol spliced in the first splicing method, which contains the firstthree-segment structure and the second three-segment structure which areconnected successively, is:

           (Formula  7) ${P_{combine}(t)} = \left\{ \begin{matrix}{P_{C - A - B}(t)} & {0 \leq t < {\begin{pmatrix}{{Len}_{B} +} \\{{Len}_{C} +} \\N_{A}\end{pmatrix}T}} \\{P_{B - C - A}\left( {t - {\begin{pmatrix}{{Len}_{B} +} \\{{Len}_{C} +} \\N_{A}\end{pmatrix}T}} \right)} & {{\begin{pmatrix}{{Len}_{B} +} \\{{Len}_{C} +} \\N_{A}\end{pmatrix}T} \leq t < {2\begin{pmatrix}{{Len}_{B} +} \\{{Len}_{C} +} \\N_{A}\end{pmatrix}T}} \\0 & {otherwise}\end{matrix} \right.$

Then, as shown in FIG. 6, the time-domain expression of the time-domainsymbol spliced in the second splicing method, which contains the secondthree-segment structure and the first three-segment structure which areconnected successively, is:

           (Formula  8) ${P_{combine}(t)} = \left\{ \begin{matrix}{P_{B - C - A}(t)} & {0 \leq t < {\begin{pmatrix}{{Len}_{B} +} \\{{Len}_{C} +} \\N_{A}\end{pmatrix}T}} \\{P_{C - A - B}\left( {t - {\begin{pmatrix}{{Len}_{B} +} \\{{Len}_{C} +} \\N_{A}\end{pmatrix}T}} \right)} & {{\begin{pmatrix}{{Len}_{B} +} \\{{Len}_{C} +} \\N_{A}\end{pmatrix}T} \leq t < {2\begin{pmatrix}{{Len}_{B} +} \\{{Len}_{C} +} \\N_{A}\end{pmatrix}T}} \\0 & {otherwise}\end{matrix} \right.$

Similarly to the case above, when the C−A−B structure and the B−C−Astructure are cascaded, the problem of fractional frequency offsetestimation failure under a dangerous delay can be solved. When thedangerous delay results in the counteraction of segment C and segment A,section CB with the first structure and section BC with the secondstructure can still be used for timing synchronization and fractionalfrequency offset estimation.

In one preferred embodiment, the lengths of segment C, segment A andsegment B in the two three-segment structures are the same, N_(A)=1024or 2048; Len_(C)=520, Len_(B)=504, only N1 is different, whenN_(A)=1024, N1_1=520, N1_2=504, and when N_(A)=2048, N1_1=1544,N1_2=1528. A first assembling result and a second assembling result arerespectively shown in FIG. 7 and FIG. 8

when N_(A)=1024, f_(SH)=1/1024T, and when N_(A)=2048, f_(SH)=1/2048T,then the time-domain expression of the first three-segment structure is:

$\begin{matrix}{{P_{C - A - B}(t)} = \left\{ {\begin{matrix}{P\; 1{\_ A}\left( {t + {504T}} \right)} & {0 \leq t < {520T}} \\{P\; 1{\_ A}\left( {t - {520T}} \right)} & {{520T} \leq t < {1544T}} \\{P\; 1{\_ A}\left( {t - {1024T}} \right)e^{j\; 2\pi \; f_{SH}t}} & {{1544T} \leq t < {2048T}} \\0 & {otherwise}\end{matrix}\mspace{79mu} {when}\mspace{14mu} \left( {N_{A} = 1024} \right)\mspace{79mu} {or}} \right.} & \left( {{Formula}\mspace{14mu} 9} \right) \\{{P_{C - A - B}(t)} = \left\{ {\begin{matrix}{P\; 1{\_ A}\left( {t + {1528T}} \right)} & {0 \leq t < {520T}} \\{P\; 1{\_ A}\left( {t - {520T}} \right)} & {{520T} \leq t < {2568T}} \\{P\; 1{\_ A}\left( {t - {1024T}} \right)e^{j\; 2\pi \; f_{SH}t}} & {{2568T} \leq t < {3072T}} \\0 & {otherwise}\end{matrix}\mspace{79mu} {when}\mspace{14mu} \left( {N_{A} = 2048} \right)} \right.} & \left( {{Formula}\mspace{14mu} 10} \right)\end{matrix}$

the time-domain expression of the second three-segment structure is:

$\begin{matrix}{{P_{B - C - A}(t)} = \left\{ {\begin{matrix}{P\; 2{\_ A}\left( {t + {504T}} \right)e^{{- j}\; 2\pi \; {f_{SH}{({t - {520T}})}}}} & {0 \leq t < {504T}} \\{P\; 2{\_ A}(t)} & {{504T} \leq t < {1024T}} \\{P\; 2{\_ A}\left( {t - {1024T}} \right)} & {{1024T} \leq t < {2048T}} \\0 & {otherwise}\end{matrix}\mspace{79mu} {when}\mspace{14mu} \left( {N_{A} = 1024} \right)\mspace{79mu} {or}} \right.} & \left( {{Formula}\mspace{14mu} 11} \right) \\{{P_{B - C - A}(t)} = \left\{ {\begin{matrix}{P\; 2{\_ A}\left( {t + {1528T}} \right)e^{{- j}\; 2\pi \; {f_{SH}{({t - {520T}})}}}} & {0 \leq t < {504T}} \\{P\; 2{\_ A}\left( {t + {1024T}} \right)} & {{504T} \leq t < {1024T}} \\{P\; 2{\_ A}\left( {t - {1024T}} \right)} & {{1024T} \leq t < {3072T}} \\0 & {otherwise}\end{matrix}\mspace{79mu} {when}\mspace{14mu} \left( {N_{A} = 1024} \right)} \right.} & \left( {{Formula}\mspace{14mu} 12} \right)\end{matrix}$

FIG. 7 is a schematic diagram of predefined processing rule based on thefirst assembling mode in the embodiments of the present invention. FIG.8 is a schematic diagram of predefined processing rule based on thesecond assembling mode in the embodiments of the present invention.

With regard to the case where a preamble symbol is assembled by twotime-domain symbols with three-segment structure, the two three-segmentstructures shown in FIG. 7 and FIG. 8 are respectively the firstthree-segment structure (CAB) and the second three-segment structure(BCA); similarly, in each time-domain symbol with a three-segmentstructure, the second part (part B, as a postfix or a hyper prefix) canbe generated by truncating the first part (part A) from different startpoints so as to transmit signalling. Only specially, when performingassembling with two different three-segment structures, the start pointN1_1 of selection for the symbol with the first three-segment structureand the selection start point N1_2 for the symbol with the secondthree-segment structure satisfy some restriction relationship:

N1_1+N1_2=2N _(A)−(Len_(B)+Len_(c))   (Formula 13)

For another example, as stated above, 1 bit of signalling is used fortransmitting emergency broadcast identifier EAS_flag. Description ismade below by utilizing table 1 and particular expressions.

TABLE 1 Corresponding table of emergency broadcast identification andselection start points for the postfix or the hyper prefix with atime-domain main body signal length predefined N_(A) = 1024, N_(A) =1024, N_(A) = 2048, N_(A) = 2048, EAS_flag = EAS_flag = EAS_flag =EAS_flag = 0 1 0 1 C-A-B N1_1 = 520 N1_1 = 504 N1_1 = 1544 N1_1 = 1528B-C-A N1_2 = 504 N1_2 = 520 N1_2 = 1528 N1_2 = 1544when EAS_flag=0, the time-domain expression of the C−A−B three-segmentstructure is:

$\begin{matrix}{{P_{C - A - B}(t)} = \left\{ {\begin{matrix}{{P1\_ A}\left( {t + {504T}} \right)} & {0 \leq t < {520T}} \\{{P1\_ A}\left( {t - {520T}} \right)} & {{520T} \leq t < {1544T}} \\{P\; 1{\_ A}\left( {t - {1024T}} \right)e^{j\; 2\pi \; f_{SH}t}} & {{1544T} \leq t < {2048T}} \\0 & {otherwise}\end{matrix}\mspace{79mu} {when}\mspace{14mu} \left( {N_{A} = 1024} \right)} \right.} & \left( {{Formula}\mspace{14mu} 14} \right) \\{{P_{C - A - B}(t)} = \left\{ {\begin{matrix}{P\; 1{\_ A}\left( {t + {1528T}} \right)} & {0 \leq t < {520T}} \\{P\; 1{\_ A}\left( {t - {520T}} \right)} & {{520T} \leq t < {2568T}} \\{P\; 1{\_ A}\left( {t - {1024T}} \right)e^{j\; 2\pi \; f_{SH}t}} & {{2568T} \leq t < {3072T}} \\0 & {otherwise}\end{matrix}\mspace{79mu} {when}\mspace{14mu} \left( {N_{A} = 2048} \right)\mspace{79mu} {and}} \right.} & \left( {{Formula}\mspace{14mu} 15} \right)\end{matrix}$

the time-domain expression of the B−C−A three-segment structure is:

$\begin{matrix}{{P_{B - C - A}(t)} = \left\{ {\begin{matrix}{{P2\_ A}\left( {t + {504T}} \right)e^{{- j}\; 2\pi \; {f_{SH}{({t - {520T}})}}}} & {0 \leq t < {504T}} \\{{P2\_ A}(t)} & {{504T} \leq t < {1024T}} \\{P\; 2{\_ A}\left( {t - {1024T}} \right)} & {{1024T} \leq t < {2048T}} \\0 & {otherwise}\end{matrix}\mspace{79mu} {when}\mspace{14mu} \left( {N_{A} = 1024} \right)\mspace{76mu} {and}} \right.} & \left( {{Formula}\mspace{14mu} 16} \right) \\{{P_{B - C - A}(t)} = \left\{ {\begin{matrix}{P\; 2{\_ A}\left( {t + {1528T}} \right)e^{{- j}\; 2\pi \; {f_{SH}{({t - {520T}})}}}} & {0 \leq t < {504T}} \\{P\; 2{\_ A}\left( {t + {1024T}} \right)} & {{504T} \leq t < {1024T}} \\{P\; 2{\_ A}\left( {t - {1024T}} \right)} & {{1024T} \leq t < {3072T}} \\0 & {otherwise}\end{matrix}\mspace{79mu} {when}\mspace{14mu} \left( {N_{A} = 2048} \right)} \right.} & \left( {{Formula}\mspace{14mu} 17} \right)\end{matrix}$

when EAS_flag=1, the time-domain expression of the C−A−B three-segmentstructure is:

$\begin{matrix}{{P_{C - A - B}(t)} = \left\{ {\begin{matrix}{{P1\_ A}\left( {t + {504T}} \right)} & {0 \leq t < {520T}} \\{{P1\_ A}\left( {t - {520T}} \right)} & {{520T} \leq t < {1544T}} \\{P\; 1{\_ A}\left( {t - {1040T}} \right)e^{j\; 2\pi \; f_{SH}t}} & {{1544T} \leq t < {2048T}} \\0 & {otherwise}\end{matrix}\mspace{79mu} {when}\mspace{14mu} \left( {N_{A} = 1024} \right)} \right.} & \left( {{Formula}\mspace{14mu} 18} \right) \\{{P_{C - A - B}(t)} = \left\{ {\begin{matrix}{P\; 1{\_ A}\left( {t + {1528T}} \right)} & {0 \leq t < {520T}} \\{P\; 1{\_ A}\left( {t - {520T}} \right)} & {{520T} \leq t < {2568T}} \\{P\; 1{\_ A}\left( {t - {1040T}} \right)e^{j\; 2\pi \; f_{SH}t}} & {{2568T} \leq t < {3072T}} \\0 & {otherwise}\end{matrix}\mspace{79mu} {when}\mspace{14mu} \left( {N_{A} = 2048} \right)\mspace{79mu} {and}} \right.} & \left( {{Formula}\mspace{14mu} 19} \right)\end{matrix}$

the time-domain expression of the B−C−A three-segment structure is:

$\begin{matrix}{{P_{B - C - A}(t)} = \left\{ {\begin{matrix}{{P1\_ A}\left( {t + {520T}} \right)e^{{- j}\; 2\; \pi \; {f_{SH}{({t - {504T}})}}}} & {0 \leq t < {504T}} \\{{P1\_ A}(t)} & {{504T} \leq t < {1024T}} \\{{P1\_ A}\left( {t - {1024T}} \right)} & {{1024T} \leq t < {2048T}} \\0 & {otherwise}\end{matrix}\mspace{79mu} {when}\mspace{14mu} \left( {N_{A} = 1024} \right)} \right.} & \left( {{Formula}\mspace{14mu} 20} \right) \\{\mspace{79mu} {and}} & \; \\{{P_{B - C - A}(t)} = \left\{ {\begin{matrix}{{P1\_ A}\left( {t + {1544T}} \right)e^{{- j}\; 2\; \pi \; {f_{SH}{({t - {504T}})}}}} & {0 \leq t < {504T}} \\{{P1\_ A}\left( {t + {1024T}} \right)} & {{504T} \leq t < {1024T}} \\{{P1\_ A}\left( {t - {1024T}} \right)} & {1024 \leq t < {3072T}} \\0 & {otherwise}\end{matrix}\mspace{79mu} {{when}{\mspace{11mu} \;}\left( {N_{A} = 2048} \right)}} \right.} & \left( {{Formula}\mspace{14mu} 21} \right)\end{matrix}$

With regard to the case where a preamble symbol is assembled by twotime-domain symbols with three-segment structure, emergency broadcastcan also be identified by different sequential orders of the twotime-domain symbols.

As stated above, on the basis of existing two three-segment symbols, thetwo symbols can be assembled; and when the assembling is performed basedon the first assembling method, it indicates that a system is offering acommon broadcast service, and when the assembling is performed based onthe second assembling method, it indicates that the system is offeringan emergency broadcast service. It is also possible that when theassembling is performed based on the first assembling method, itindicates that a system is offering an emergency broadcast service, andwhen the assembling is performed based on the second assembling method,it indicates that the system is offering a common broadcast service.

The preamble symbol (preamble) or bootstrap introduced above containsnot only: a time-domain symbol with a first three-segment structure; ora time-domain symbol with a second three-segment structure; or a unitedsymbol assembled by the first three-segment structure and the secondthree-segment structure; but also contains a free combination of severaltime-domain symbols with the first three-segment structure and/orseveral time-domain symbols with the second three-segment structurearranged in any order. That is, the preamble symbol or bootstrap canonly contains CAB or BCA, can also contain a combination of several CABor several BCA, and can also be a free combination of an unlimitednumber of CAB and an unlimited number of BCA arranged in any order. Itshould be specially noted that the preamble symbol of bootstrap in thepresent invention is not limited to only containing a C−A−B or B−C−Astructure, but can also contain other time-domain structures, such as atraditional CP structure.

It has been mentioned above that, when the C−A−B structure and the B−C−Astructure are cascaded, the problem of fractional frequency offsetestimation failure under a dangerous delay can be solved. When thedangerous delay results in the counteraction of segment C and segment A,section CB with the first structure and section BC with the secondstructure can still be used for timing synchronization and small offsetestimation. Therefore, in the preferred embodiment, when the preamblesymbol contains at least two time-domain symbols with a three-segmentstructure, it generally at least contains a cascade of a C−A−B structureand a B−C−A structure.

Specifically, the number of time-domain symbols contained in thepreamble symbols is set to four, and some preferable spliced structuresof four time-domain symbols are given below, which are successivelyarranged into any one of the following structures:

(1) C−A−B, B−C−A, C−A−B, B−C−A; or

(2) C−A−B, B−C−A, B−C−A, B−C−A; or

(3) B−C−A, C−A−B, C−A−B, C−A−B; or

(4) C−A−B, B−C−A, C−A−B, C−A−B; or

(5) C−A−B, C−A−B, C−A−B, B−C−A; or

(6) C−A−B, C−A−B, C−A−B, C−A−B or

(7) C−A−B, C−A−B, B−C−A, B−C−A.

A structure of four time-domain symbols like C−A−B, B−C−A, C−A−B, B−C−Afor example makes the most of the effect of cascading. A structure offour time-domain symbols like C−A−B, B−C−A, B−C−A, B−C−A for examplestretches the guard interval for part A of the sequential symbol, andthe first symbol is generally a known signal; therefore, C−A−B isadopted.

The number of time-domain symbols is not limited to four, now aparticular embodiment in which the first time-domain has a C−A−Bthree-segment structure, and the three-segment structures after that areall B−C−A connected successively is given below. Let the total number ofthe time-domain symbols containing the first or the second three-segmentstructure in the preamble symbol or bootstrap be M.

Then the time-domain expression of the M time-domain symbols with athree-segment structure which are assembled is:

$\begin{matrix}{{P_{antine}(t)} = \left\{ {{\begin{matrix}{P_{C - A - B}(t)} & {0 \leq t < {\left( {{Len}_{B} + {Len}_{C} + N_{A}} \right)T}} \\\begin{matrix}{P_{B - C - A}\left( {t - {1*}} \right.} \\\left. {\left( {{Len}_{B} + {Len}_{C} + N_{A}} \right)T} \right)\end{matrix} & \begin{matrix}{{i*\left( {{Len}_{B} + {Len}_{C} + N_{A}} \right)T} \leq t <} \\{\left( {i + 1} \right)*\left( {{Len}_{B} + {Len}_{C} + N_{A}} \right)T}\end{matrix} \\0 & {otherwise}\end{matrix}1} \leq i < {M - 1}} \right.} & \left( {{Formula}\mspace{14mu} 22} \right)\end{matrix}$

The present invention also provides a frequency-domain symbol generationmethod, and description is made below to a method for generating afrequency-domain OFDM symbol with the following frequency-domainstructure I and a frequency-domain OFDM symbol with the followingfrequency-domain structure II respectively.

Furthermore, it can be seen in combination with the three-segmenttime-domain structure above that a fixed corresponding relationshipexists between the time domain and the frequency domain. In a generalcase, a time-domain main body signal (part A) is a time-domain OFDMsymbol formed from a frequency-domain OFDM symbol after inverse Fouriertransform. However, it should be noted that the frequency-domain symbolgeneration method provided in the present invention is not limited to beused in a symbol in which the three-segment structure as shown in FIG. 1to FIG. 8 above is adopted in terms of the time domain, but can also beapplied to other symbols with an arbitrary time-domain structure.

It is assumed that P1_X is a corresponding frequency-domain OFDM symbol,and inverse discrete Fourier transform is performed on P1_X_(i) toobtain a time-domain OFDM symbol:

$\begin{matrix}{{{{P1\_ A}(t)} = {\frac{1}{\sqrt{M}}{\sum\limits_{m = 0}^{N_{FFT}}\; {{P1\_ X}(m)e^{j\; 2\; \pi \frac{({m - {N_{FFT}/2}})}{N_{FFT}T}t}}}}},} & \left( {{Formula}\mspace{14mu} 23} \right)\end{matrix}$

where M is the sum of the power for valid non-zero subcarriers.

In the present invention, the frequency-domain structures of twodifferent types of P1_X are elaborated.

[Frequency-Domain Structure I]

First of all, the frequency-domain structure of the first type of P1_Xis elaborated, and is defined as frequency-domain structure I. Forfrequency-domain structure I, the frequency-domain symbol generationmethod comprises the following steps:

respectively generating a fixed sequence and a signalling sequence onthe frequency domain; and

arranging the fixed sequence and the signalling sequence and fillingvalid subcarriers with the arranged fixed sequence and signallingsequence, for forming a frequency-domain symbol.

For frequency-domain structure I of P1_X, the frequency-domain OFDMsymbol respectively comprises three parts, i.e. virtual subcarriers,signalling sequence (referred to as SC) subcarriers and fixed sequence(referred to as FC) subcarriers.

After arranging signalling sequence subcarriers and fixed sequencesubcarriers according to a predefined interlaced arrangement rule, thevirtual subcarriers are distributed at two sides of them. The predefinedinterlaced arrangement rule comprises either one of the following tworules:

a first predefined interlaced arrangement rule: arrangement in anodd-even interlaced manner or an even-odd interlaced manner; and

a second predefined interlaced arrangement rule: placing a portion ofthe signalling sequence on odd-numbered subcarriers, and the otherportion of the signalling sequence on even-numbered subcarriers; andplacing a portion of the fixed sequence on the odd-numbered subcarriers,and the other portion of the fixed sequence on the even-numberedsubcarriers.

The first predefined interlaced arrangement rule is to arrange the SCand the FC in an odd-even interlaced pattern or an even-odd interlacedpattern, in this way, the FC is arranged according to a pilor rule. Inthe second predefined interlaced arrangement rule, a part of the SCsequence needs to be put on odd-numbered subcarriers, and the remainingSC sequence is put on even-numbered subcarriers; and a part of the FCsequence needs to be put on odd-numbered subcarriers, and the remainingFC sequence is put on even-numbered subcarriers; in this way, the casewhere the entire FC or SC is put on odd-numbered or even-numberedsubcarriers and would entirely fade under some special multipath channelis avoided, and this arrangement would not increase the complexity ofchannel estimation, and is thus a better choice.

Let the length of the fixed sequence be L (that is, the number of validsubcarriers bearing the fixed sequence is L), and the length of thesignalling sequence be P (that is, the number of valid subcarriersbearing the signalling sequence is P). In this embodiment, L=P. Itshould be noted that when the length of the fixed sequence is notconsistent with that of the signalling sequence (e.g. P>L), theinterlaced arrangement of the fixed sequence and the signalling sequenceaccording to the above-mentioned rule can be realized by means offilling subcarriers with zero sequence.

FIG. 9 is a schematic diagram of the signalling sequence subcarriers,the fixed sequence subcarriers and the virtual subcarriers arrangedaccording to a first predetermined interlaced arrangement rule in theembodiments of the present invention.

As shown in FIG. 9, in this preferred implementation, the stepcomprises: respectively filling subcarriers with certain zero sequenceat two sides of the valid subcarriers, to form a frequency-domain OFDMsymbol with a predefined length.

Corresponding to the fact that the length N_(A) of the time-domain mainbody signal A in the above-mentioned time-domain structure is 1024, thelength of frequency domain signal N_(FFT) formed by performing fastFourier transform (FFT) is 1024.

The example of the predefined length of N_(FFT) being 1024 is continuedto be used below, the length of the zero sequence subcarriers isG=1024−L−P, and (1024−L−P)/2 zero sequence subcarriers are used forfilling subcarriers at two sides thereof. For example, L=P=353, thenG=318, 159 zero sequence subcarriers are respectively filled at twosides.

Generating the frequency-domain OFDM symbol according to the firstpredefined interlaced arrangement rule comprises the following step:

The (11)th fixed sequence generation step: the fixed sequence iscomposed of 353 complex numbers, the modulus thereof is constant, andthe nth value of the fixed sequence subcarriers is expressed as:

FC(n)=√{square root over (R)}e^(jω) ^(n) , n=0˜352   (Formula 24)

where R is the power ratio of FC to SC, and the modulus SC, is constant1.

$\begin{matrix}{R = \frac{\sum\limits_{n}\; {{{FC}(n)}}^{2}}{\sum\limits_{n}\; {{{SC}(n)}}^{2}}} & \left( {{Formula}\mspace{14mu} 25} \right)\end{matrix}$

The radian value ω_(n) of the fixed sequence subcarriers is determinedthrough the first predefined fixed subcarrier radian values in table 2.

TABLE 2 The first predefined fixed subcarrier radian value table (firstpredefined interlaced arrangement rule) 5.43 2.56 0.71 0.06 2.72 0.771.49 6.06 4.82 2.10 5.62 4.96 4.93 4.84 4.67 5.86 5.74 3.54 2.50 3.750.86 1.44 3.83 4.08 5.83 1.47 0.77 1.29 0.16 1.38 4.38 2.52 3.42 3.464.39 0.61 4.02 1.26 2.93 3.84 3.81 6.21 3.80 0.69 5.80 4.28 1.73 3.343.08 5.85 1.39 0.25 1.28 5.14 5.54 2.38 6.20 3.05 4.37 5.41 2.23 0.495.12 6.26 3.00 2.60 3.89 5.47 4.83 4.17 3.36 2.63 3.94 5.13 3.71 5.890.94 1.38 1.88 0.13 0.27 4.90 4.89 5.50 3.02 1.94 2.93 6.12 5.47 6.041.14 5.52 2.01 1.08 2.79 0.74 2.30 0.85 0.58 2.25 5.25 0.23 6.01 2.662.48 2.79 4.06 1.09 2.48 2.39 5.39 0.61 6.25 2.62 5.36 3.10 1.56 0.910.08 2.52 5.53 3.62 2.90 5.64 3.18 2.36 2.08 6.00 2.69 1.35 5.39 3.542.01 4.88 3.08 0.76 2.13 3.26 2.28 1.32 5.00 3.74 1.82 5.78 2.28 2.444.57 1.48 2.48 1.52 2.70 5.61 3.06 1.07 4.54 4.10 0.09 2.11 0.10 3.183.42 2.10 3.50 4.65 2.18 1.77 4.72 5.71 1.48 2.50 4.89 4.04 6.12 4.281.08 2.90 0.24 4.02 1.29 3.61 4.36 6.00 2.45 5.49 1.02 0.85 5.58 2.430.83 0.65 1.95 0.79 5.45 1.94 0.31 0.12 3.25 3.75 2.35 0.73 0.20 6.052.98 4.70 0.69 5.97 0.92 2.65 4.17 5.71 1.54 2.84 0.98 1.47 6.18 4.524.44 0.44 1.62 6.09 5.86 2.74 3.27 3.28 0.55 5.46 0.24 5.12 3.09 4.664.78 0.39 1.63 1.20 5.26 0.92 5.98 0.78 1.79 0.75 4.45 1.41 2.56 2.551.79 2.54 5.88 1.52 5.04 1.53 5.53 5.93 5.36 5.17 0.99 2.07 3.57 3.672.61 1.72 2.83 0.86 3.16 0.55 5.99 2.06 1.90 0.60 0.05 4.01 6.15 0.100.26 2.89 3.12 3.14 0.11 0.11 3.97 5.15 4.38 2.08 1.27 1.17 0.42 3.473.86 2.17 5.07 5.33 2.63 3.20 3.39 3.21 4.58 4.66 2.69 4.67 2.35 2.440.46 4.26 3.63 2.62 3.35 0.84 3.89 4.17 1.77 1.47 2.03 0.88 1.93 0.803.94 4.70 6.12 4.27 0.31 4.85 0.27 0.51 2.70 1.69 2.18 1.95 0.02 1.913.13 2.27 5.39 5.45 5.45 1.39 2.85 1.41 0.36 4.34 2.44 1.60 5.70 2.603.41 1.84 5.79 0.69 2.59 1.14 5.28 3.72 5.55 4.92 2.64

The (12)th signalling sequence generation step: the signalling sequencegeneration step contains two methods, i.e. a first signalling sequencegeneration method and a second signalling sequence generation methoddescribed below. In this embodiment, either one of the following twomethods can be used to generate a signalling sequence in the frequencydomain, and the two particular methods for generating a signallingsequence are described in detail below.

A first signalling sequence generation method:

1.1 Determine the length and number of a signalling sequence;

1.2 Determine the root value in a CAZAC sequence generation formulabased on the length and number of the signalling sequence, wherein thelength of the signalling sequence is smaller than or equal to the rootvalue, and the root value is greater than or equal to twice of thenumber of the signalling sequence. Preferably, the root value isselected as the length of the signalling sequence.

For example, the length (L) of the sequence and the number of signallingare determined. For example, if N bits are to be transmitted, then thenumber (num) of signalling is 2^(N), and a root of CAZAC sequence ischosen to generate the exp(jπqn(n+1)/root) in the formula. The length(L) of the sequence is smaller than or equal to the root value, and theroot value is greater than or equal to 2*num. Generally, the root valueis a prime number.

1.3 Select different q values for generating CAZAC sequences, whereinthe number of q values is equal to the number of the signallingsequence, and the sum of any two q values is not equal to the rootvalue; and the generated CAZAC sequences should be performed cyclicshift on, and the number of the cyclic shift is determined by thecorresponding root value and q value.

For example, value of num different q₀, q₁, . . . , q_(num−1) are chosento generate the CAZAC sequence:

s(n)=exp(jπqn(n+1)/root), n=0, . . . root−1,   (Formula 26)

after the cyclic shift, the sequence is:

s _(k)(n)=(k), s(k+1), . . . , s(L−1), s(0), . . . , s(k−1)]  (Formula27)

where k is the value of the cyclic shift.

It should be noted that, in this embodiment, q_(i)(0≦i≦num−1) selectedshould satisfy the following condition: any two q_(i) and q_(j)(0≦i,j≦num−1) satisfy q_(i)+q_(j)≠root.

Under the above-mentioned condition, a sequence enabling the PAPR of theoverall frequency-domain OFDM symbol to be lower is preferably selected.Moreover, if L is greater than or equal to 2*num, it is preferablyselected that root=L. As such, the auto-correlation value of thesequence is zero.

1.4 Select the signalling sequence from all the CAZAC sequencesaccording to the determined number of signalling sequences. It should benoted that if L=root, then truncation is not required, and the obtainedCAZAC sequences can be taken as signalling sequences directly.

For example a continuous partial sequence with a length of L truncatedfrom each sequence among the num sequences, or the entire sequence istaken as a signalling sequence.

By way of example, the signalling sequence has a length of L=353 and anumber of num=128, then the root can be selected as the closest primenumber 353. The value range of q is 1 to 352, and the value range of thecyclic shift value of each sequence is 1 to 353. Among all theselectable signalling sequences, the following 128 sets are preferablyselected, the q values and the cyclic shift digits thereof are as shownin q value table of table 3 and cyclic shift digit table of table 4:

TABLE 3 q value table 1 9 10 16 18 21 28 29 32 35 49 51 53 54 55 57 5960 61 65 68 70 74 75 76 77 78 82 84 85 86 88 90 95 96 103 113 120 123125 126 133 134 135 137 138 140 141 142 145 147 148 150 151 155 156 157161 163 165 167 170 176 178 179 181 182 184 185 187 194 200 201 204 209210 217 222 223 224 225 229 232 234 235 237 239 241 244 246 247 248 249251 252 253 254 255 262 270 272 273 280 282 290 291 306 307 308 309 311313 314 315 317 320 326 327 330 331 333 336 338 340 342 345 347 349

TABLE 4 Cyclic shift value table 105 244 172 249 280 251 293 234 178 1163 217 83 111 282 57 85 134 190 190 99 180 38 191 22 254 186 308 178 251277 261 44 271 265 298 328 282 155 284 303 113 315 299 166 342 133 115225 13 26 326 148 195 145 185 121 58 162 118 151 182 230 39 249 305 309144 188 181 265 140 212 137 10 298 122 281 181 267 178 187 177 352 4 353269 38 342 288 277 88 124 120 162 204 174 294 166 157 56 334 110 183 131171 166 321 96 37 261 155 34 149 156 267 332 93 348 300 245 101 186 117329 352 215 55A second signalling sequence generation method:

2.1 Determine the length and number of a signalling sequence;

2.2 Determine several root values in a CAZAC sequence generation formulabased on the length and number of the signalling sequence, wherein thelength of the signalling sequence is smaller than or equal to theminimum value in the selected several root values, and the sum of theselected several root values is greater than or equal to twice of thenumber of the signalling sequence. Preferably, the root value isselected as the length of the signalling sequence.

For example, the length (L) of the sequence and the number of signallingare determined. For example, if N bits are to be transmitted, then thenumber (num) of signalling is 2^(N), and a CAZAC sequence is chosen togenerate K root_(k) (0≦k≦K−1) in the formula exp(jπqn(n+1)/root). Thelength (L) of the signalling sequence is smaller than or equal to theminimum value in root_(k), and the sum of several root_(k) is greaterthan or equal to 2*num, i.e.

${\sum\limits_{k = 0}^{K - 1}\; {root}_{k}} \geq {2^{*}{{num}.}}$

Generally, the value of root_(k) is a prime number.

2.3 For each root value, select different q values for generating CAZACsequences, wherein the number of q values is smaller than or equal to ½of the corresponding root value, and the sum of any two q values is notequal to the corresponding root value; and the generated CAZAC sequencesshould be performed cyclic shift on, and the value of the cyclic shiftis determined by the corresponding root value and q value.

For example, for each root_(k)(0≦k≦K−1), num_(k) different q₀, q₁, andq_(num) _(k) ⁻¹ are chosen to the produce CAZAC sequencesexp(jπqn(n+1)/root_(k)), n=0, . . . root_(k)−1, where

${{num}_{k} \leq \left\lfloor \frac{{root}_{k}}{2} \right\rfloor},\; {{{and}\mspace{14mu} {\sum\limits_{k = 0}^{K - 1}\; {num}_{k}}} = {{num}.}}$

In the second signalling sequence generation method, for each rootvalue, different q values are chosen to generate the CAZAC sequences,and the generated CAZAC sequences should be performed cyclic shift on,which can refer to the description about method I above, and will not bedescribed herein.

It should be noted that, in this embodiment, q_(i)(0≦i≦num_(k)−1)selected should satisfy the following condition: any two q_(i) andq_(j)(0≦i, j≦num_(k)−1) satisfy q_(i)+q_(j)≠root_(k).

Under the above-mentioned condition, a sequence enabling the PAPR of theoverall frequency-domain OFDM symbol to be lower is preferably selected.Moreover, it can be preferentially selected that one root=L. As such,the auto-correlation value of the sequence generated by this root iszero.

2.4 Select the signalling sequence from each CAZAC sequence according tothe determined number of signalling sequences. It is worth emphasizingthat, if some root=L, then the signalling sequence is determined usingthe CAZAC sequence generated by the root value which is the length ofthe signalling sequence.

For example a continuous partial sequence with a length of L cyclicallytruncated from each sequence among the num sequences, or the entiresequence is taken as a signalling sequence.

By way of example, L=353, num=128. According to the first signallingsequence generation method, it is preferentially selected that the rootis 353. Then, it is selected that q=1,2, . . . 128, and satisfiesq_(i)+q_(j)≠353, (0≦i, j≦128−1). Finally, cyclically truncating eachsequence with a length of 353.

For another example, L=350, num=256. According to the second signallingsequence generation method, it is preferentially selected that the root1is 353 and root2=359, and then for root1=353, 128 sequences are selectedin total, i.e. q=1,2,3, . . . 128, q_(i)+q_(j)≠353. Then for root2=359,128 sequences are selected in total, i.e. q=100, 101, 102, . . . 227; tothis end, there are 256 sequences in total. Finally, cyclicallytruncating each sequence with a length of 353.

In the following, in the (12)th signalling sequence generation step, 512signalling sequences are generated in total by means of the secondsignalling sequence generation method, i.e. Seq₀, Seq₁, . . . , Seq₅₁₁;then obtaining the opposite number of each signalling sequenceSeq₀˜Seq₅₁₁, namely, Seq₀˜−Seq₅₁₁; the receiving end differentiates apositive sequence from a negative according to whether a correlationvalue is positive or negative, which means 10 bits of signallinginformation is conveyed in total. The 512 signalling sequences can befurther divided into 4 groups, each group including 128 signallingsequences. The substeps of generating each group of 128 signallingsequences are as follows:

The first substep: generating a reference sequence zc_(i)(n), which is aZadoff-Chu sequence zc(n) with a length of N:

$\begin{matrix}{{{{zc}_{i}(n)} = e^{{- j}\; \pi \frac{u_{i}{n{({n + 1})}}}{N}}},{n = {{0\text{\textasciitilde}N} - 1}},{i = {0\text{\textasciitilde}127}}} & \left( {{Formula}\mspace{14mu} 28} \right)\end{matrix}$

The second substep: zc*_(i)(n) with a length of 2N is produced bycopying zc_(i)(n) twice:

$\begin{matrix}{{{zc}_{i}^{*}(n)} = \left\{ {\begin{matrix}{{{zc}_{i}(n)},{0 \leq n < N}} \\{{{zc}_{i}\left( {n - N} \right)},{N \leq n < {2N}}}\end{matrix},{n = {{0\text{\textasciitilde}N} - 1}},{i = {0\text{\textasciitilde}127}}} \right.} & \left( {{Formula}\mspace{14mu} 29} \right)\end{matrix}$

The third substep: truncating a sequence with a length of 353 from aspecific start position k_(i) in zc*_(i)(n), to produce SC_(i)(n):

SC _(i)(n)=zc* _(i)(k _(i)−1+n), n=0˜352   (Formula 30)

The N value, u_(i) and shift value k_(i) of each group of signallingsequences Seq₀˜Seq₁₂₇ are respectively determined from variouscorresponding predefined signalling sequence parameter tables below,i.e. table 5 to table 8.

The N value, u_(i) and shift value k_(i) of the first group of sequencesSeq₀˜Seq₁₂₇ are as shown in table 5 below.

TABLE 5 The first group of signalling sequence parameters N 353 u_(i), i= 0-127 1, 9, 10, 16, 18, 21, 28, 29, 32, 35, 49, 51, 53, 54, 55, 57,59, 60, 61, 65, 68, 70, 74, 75, 76, 77, 78, 82, 84, 85, 86, 88, 90, 95,96, 103, 113, 120, 123, 125, 126, 133, 134, 135, 137, 138, 140, 141,142, 145, 147, 148, 150, 151, 155, 156, 157, 161, 163, 165, 167, 170,176, 178, 179, 181, 182, 184, 185, 187, 194, 200, 201, 204, 209, 210,217, 222, 223, 224, 225, 229, 232, 234, 235, 237, 239, 241, 244, 246,247, 248, 249, 251, 252, 253, 254, 255, 262, 270, 272, 273, 280, 282,290, 291, 306, 307, 308, 309, 311, 313, 314, 315, 317, 320, 326, 327,330, 331, 333, 336, 338, 340, 342, 345, 347, 349 k_(i), i = 0-127 105,244, 172, 249, 280, 251, 293, 234, 178, 11, 63, 217, 83, 111, 282, 57,85, 134, 190, 190, 99, 180, 38, 191, 22, 254, 186, 308, 178, 251, 277,261, 44, 271, 265, 298, 328, 282, 155, 284, 303, 113, 315, 299, 166,342, 133, 115, 225, 13, 26, 326, 148, 195, 145, 185, 121, 58, 162, 118,151, 182, 230, 39, 249, 305, 309, 144, 188, 181, 265, 140, 212, 137, 10,298, 122, 281, 181, 267, 178, 187, 177, 352, 4, 353, 269, 38, 342, 288,277, 88, 124, 120, 162, 204, 174, 294, 166, 157, 56, 334, 110, 183, 131,171, 166, 321, 96, 37, 261, 155, 34, 149, 156, 267, 332, 93, 348, 300,245, 101, 186, 117, 329, 352, 215, 55

The generation steps of the second group of sequences Seq₁₂₈˜Seq₂₅₅ arethe same as those of the first group, and the N value, u_(i) and shiftvalue k_(i) of thereof are as shown in table 6 below.

TABLE 6 The second group of signalling sequence parameters N 367 u_(i),i = 0-127 8, 9, 10, 15, 19, 21, 31, 34, 39, 49, 58, 59, 71, 76, 80, 119,120, 121, 123, 140, 142, 151, 154, 162, 166, 171, 184, 186, 188, 190,191, 193, 194, 195, 198, 203, 204, 207, 208, 209, 210, 211, 212, 214,215, 219, 220, 221, 222, 223, 224, 226, 228, 230, 232, 233, 235, 236,237, 239, 240, 241, 243, 245, 249, 250, 252, 254, 257, 259, 260, 261,262, 263, 264, 265, 266, 267, 269, 271, 272, 273, 275, 276, 277, 278,281, 282, 283, 284, 285, 286, 289, 294, 297, 299, 302, 303, 306, 307,310, 311, 312, 313, 314, 316, 317, 321, 322, 323, 326, 327, 329, 331,332, 334, 338, 340, 342, 344, 345, 347, 349, 351, 356, 361, 363, 366k_(i), i = 0-127 198, 298, 346, 271, 345, 324, 160, 177, 142, 71, 354,290, 69, 144, 28, 325, 100, 55, 237, 196, 271, 210, 187, 277, 8, 313,53, 53, 194, 294, 36, 202, 69, 25, 18, 179, 318, 149, 11, 114, 254, 191,226, 138, 179, 341, 366, 176, 64, 50, 226, 23, 181, 26, 327, 141, 244,179, 74, 23, 256, 265, 223, 288, 127, 86, 345, 304, 260, 139, 312, 62,360, 107, 201, 301, 263, 257, 184, 329, 300, 81, 121, 49, 196, 201, 94,147, 346, 179, 59, 212, 83, 195, 145, 3, 119, 152, 310, 31, 134, 54,187, 131, 63, 276, 294, 142, 246, 54, 181, 121, 273, 276, 36, 47, 16,199, 243, 235, 194, 348, 95, 262, 52, 210, 115, 250

The generation steps of the third group of sequences Seq₂₅₆˜Seq₃₈₃ arethe same as those of the first group, and the N value, u_(i) and shiftvalue k_(i) of thereof are as shown in table 7 below.

TABLE 7 The third group of signalling sequence parameters N 359 u_(i), i= 0-127 1, 3, 5, 6, 9, 12, 14, 22, 29, 30, 32, 34, 60, 63, 65, 67, 72,74, 76, 78, 83, 84, 87, 88, 89, 90, 91, 92, 94, 95, 96, 99, 112, 115,123, 124, 128, 137, 141, 143, 145, 149, 152, 153, 154, 155, 159, 164,165, 169, 175, 179, 183, 186, 187, 188, 189, 192, 197, 199, 201, 202,203, 211, 215, 219, 220, 221, 223, 226, 227, 228, 229, 230, 234, 237,238, 239, 243, 246, 248, 249, 250, 252, 254, 257, 258, 261, 262, 273,274, 280, 282, 284, 286, 288, 290, 297, 298, 300, 303, 308, 309, 310,312, 313, 314, 317, 318, 319, 320, 321, 322, 323, 324, 326, 333, 334,335, 336, 339, 341, 342, 344, 349, 351, 352, 355 k_(i), i = 0-127 300,287, 80, 119, 68, 330, 93, 359, 17, 93, 355, 308, 106, 224, 20, 18, 226,165, 320, 339, 352, 316, 241, 336, 119, 166, 258, 273, 302, 275, 46, 26,259, 330, 206, 46, 10, 308, 165, 195, 314, 330, 208, 148, 275, 15, 214,251, 8, 27, 264, 169, 128, 207, 21, 246, 14, 291, 345, 114, 306, 179,109, 336, 322, 149, 270, 253, 207, 152, 26, 190, 128, 137, 196, 268, 36,40, 253, 29, 264, 153, 221, 341, 116, 24, 55, 60, 171, 25, 100, 202, 37,93, 115, 174, 239, 148, 170, 37, 328, 37, 253, 237, 355, 39, 288, 225,223, 140, 163, 145, 264, 75, 29, 282, 252, 270, 30, 262, 271, 305, 122,78, 27, 127, 92, 6

The generation steps of the fourth group of sequences Seq₃₈₄˜Seq₅₁₁ arethe same as those of the first group, and the N value, u_(i) and shiftvalue k_(i) of thereof are as shown in table 8 below.

TABLE 8 The fourth group of signalling sequence parameters N 373 u_(i),i = 0-127 26, 28, 29, 34, 38, 40, 43, 49, 54, 57, 58, 62, 64, 65, 79,80, 81, 83, 85, 86, 87, 101, 102, 187, 189, 190, 191, 193, 194, 195,196, 198, 199, 200, 202, 204, 205, 206, 208, 209, 211, 213, 214, 216,217, 218, 219, 220, 221, 222, 223, 224, 225, 227, 228, 230, 232, 233,236, 237, 241, 243, 245, 246, 247, 248, 249, 250, 251, 252, 253, 255,256, 259, 260, 261, 262, 263, 265, 266, 267, 275, 276, 280, 282, 283,284, 285, 289, 295, 297, 300, 301, 302, 303, 305, 307, 317, 320, 322,323, 325, 327, 328, 332, 338, 341, 342, 343, 348, 349, 351, 352, 353,355, 356, 357, 358, 359, 360, 361, 362, 363, 364, 367, 369, 370, 372k_(i), i = 0-127 333, 337, 177, 125, 169, 270, 254, 88, 123, 310, 96,273, 120, 239, 157, 224, 62, 119, 19, 235, 136, 117, 237, 100, 244, 181,295, 249, 356, 9, 289, 139, 82, 171, 178, 292, 158, 308, 257, 42, 55,210, 320, 294, 100, 75, 79, 163, 195, 80, 303, 97, 271, 179, 359, 178,241, 281, 367, 58, 91, 7, 179, 39, 267, 245, 213, 286, 349, 172, 35,301, 361, 102, 301, 155, 1, 34, 96, 293, 202, 87, 176, 248, 319, 301,168, 280, 154, 244, 215, 370, 260, 117, 30, 329, 42, 149, 112, 125, 50,249, 197, 273, 230, 13, 142, 244, 335, 57, 21, 261, 48, 370, 110, 296,326, 224, 77, 112, 31, 262, 121, 38, 283, 323, 93, 94

In the (13)th arrangement and filling step, the fixed sequences andsignalling sequences obtained from the (11)th step and the (12)th stepare in an odd-even interlaced arrangement, and after filling virtualsubcarriers, the frequency-domain OFDM symbols are formed according tothe following formula,

$\begin{matrix}{{{P1\_ X}(m)} = \left\{ \begin{matrix}0 & {{m = 0},1,\ldots \;,158} \\{{SC}\left( \frac{m - 159}{2} \right)} & {{m = 159},161,163,{\ldots \mspace{14mu} 863}} \\{{FC}\left( \frac{m - 160}{2} \right)} & {{m = 160},162,164,{\ldots \mspace{14mu} 864}} \\0 & {{m = 865},866,{\ldots \mspace{14mu} 1023}}\end{matrix} \right.} & \left( {{Formula}\mspace{14mu} 31} \right)\end{matrix}$

FIG. 10 is a schematic diagram of the signalling sequence subcarriers,the fixed sequence subcarriers and the virtual subcarriers arrangedaccording to a second predetermined interlaced arrangement rule in theembodiments of the present invention.

As shown in FIG. 10, a first half part of the signalling sequence at theleft side of the dashed line in the figure is placed on odd-numberedsubcarriers, and the other half part of the signalling sequence at theright side of the dashed line in the figure is placed on even-numberedsubcarrier; and a first half part of the fixed sequence at the left sideof the dashed line is placed on even-numbered subcarriers, and thelatter half part of the fixed sequence at the right side of the dashedline is placed on odd-numbered subcarrier. That is to say, P1_X₀, P1_X₁,. . . , P1_X₁₀₂₃ is generated according to the second predefinedinterlaced arranged rule; in the first half part, the SC is placed atodd-numbered carriers, and the FC is placed at even-numbered carrier;and in the later half part, the SC is placed at even-numbered carriers,and the FC is placed at odd-numbered carriers. The odd-even positions ofthe signalling sequence and the fixed sequence in the first and thelatter half part are interchanged. The odd-even positions of such fixedsequence subcarriers FC and signalling sequence subcarriers SC can beinterchanged, without any influence on the transmission performance.

When filling virtual carriers, i.e. zero sequence subcarriers, thelength of the zero sequence subcarriers filled at the left and the rightside can also be different, but are inappropriate to be far differentfrom each other.

Particularly optimized embodiments of frequency-domain symbols generatedaccording to the second predefined interlaced arrangement rule are givenbelow continuously. Generating the frequency-domain OFDM symbolaccording to the second predefined interlaced arrangement rule comprisesthe following step:

The (21)th fixed sequence generation step: this fixed sequencegeneration step is the same as the above-mentioned (11)th fixed sequencegeneration step, and only the value of the fixed sequence subcarriersradian value ω_(n) is determined through a second predefined fixedsubcarrier radian value table. The second predefined fixed subcarrierradian value table is as shown in table 9.

TABLE 9 The fixed subcarrier radian value table (according to the secondpredefined interlaced arrangement rule) 0.63 2.34 5.57 6.06 0.55 5.682.20 1.58 2.23 4.29 1.80 3.89 4.08 2.41 5.06 0.10 4.49 4.15 4.99 6.180.86 4.31 3.08 0.73 1.67 5.03 4.26 1.73 5.58 2.74 5.06 1.23 1.67 1.312.19 5.90 2.13 3.63 3.90 0.73 4.13 5.90 5.00 1.78 6.10 2.45 2.00 3.611.72 5.90 4.07 0.39 4.72 2.73 4.67 3.56 4.13 3.07 3.74 4.87 1.54 4.281.88 2.96 3.07 4.13 1.97 5.69 4.45 2.07 6.05 4.88 3.39 2.55 5.83 1.861.65 4.23 0.46 3.24 1.39 0.19 0.66 4.13 4.83 2.26 2.19 3.06 5.66 0.665.19 5.04 4.62 3.64 0.66 3.52 1.18 4.18 5.93 5.51 1.05 2.18 5.87 1.270.92 0.66 5.75 0.16 5.04 0.54 5.68 0.13 4.76 0.56 1.57 1.59 4.50 3.180.82 3.84 4.39 5.53 2.25 3.20 4.04 6.03 4.41 0.32 1.39 5.06 4.67 3.204.63 0.88 6.00 3.99 0.31 3.72 4.17 3.37 4.77 0.30 4.85 2.65 0.88 3.131.77 6.05 0.46 1.93 4.25 1.47 6.12 1.18 3.19 3.00 2.88 5.43 1.01 2.962.16 1.17 4.77 6.07 5.32 3.55 1.64 4.35 5.10 3.87 2.79 4.57 0.51 3.272.42 1.52 1.40 0.19 0.35 4.96 6.04 4.90 5.47 5.55 1.40 1.91 4.62 4.222.11 4.14 2.33 2.75 2.68 2.06 4.86 0.34 0.47 3.13 2.97 0.05 5.75 1.516.22 2.48 5.10 5.20 2.18 2.31 4.29 3.09 3.93 5.47 3.22 1.84 4.67 1.353.04 0.60 0.62 5.09 6.04 5.39 2.71 2.47 1.86 2.69 1.75 4.94 5.98 1.085.99 3.84 3.67 5.53 1.59 5.60 1.22 5.35 4.44 2.72 5.97 5.08 2.32 0.134.52 2.18 1.36 5.72 4.76 2.98 5.30 1.71 4.31 2.05 1.68 4.61 3.86 2.525.36 2.39 3.29 1.47 6.05 0.48 5.57 1.29 4.88 5.97 0.53 0.88 5.43 2.123.97 2.61 2.51 0.50 6.00 5.86 5.35 1.15 5.38 4.42 5.05 0.96 2.41 4.840.79 4.99 0.51 1.32 5.09 1.33 2.83 2.27 4.36 0.53 5.89 4.98 5.33 2.122.35 0.59 1.94 1.65 4.44 2.99 4.37 0.01 1.64 0.08 5.34 4.09 2.14 3.313.69 1.38 5.95 3.31 2.44 4.81 4.03 4.80 0.39 3.28 4.57 0.30 4.66 2.214.22 2.20 3.98 4.78 3.97 6.17 5.59 2.78 5.92 3.61 1.41 0.88 5.24 5.472.38 2.42 3.22 5.38 5.02 5.10 3.06 2.43 1.51 4.52 4.85

The (22)th signalling sequence generation step: this signalling sequencegeneration step is the same as the above-mentioned (12)th signallingsequence generation step.

The (23)th arrangement and filling step: the signalling sequences andfixed sequences obtained from the (21)th step and the (22)th step are inan odd-even and then even-odd interlaced arrangement, and after fillingzero subcarriers at the left and the right side thereof, thefrequency-domain OFDM symbols are formed according to the followingformula,

$\begin{matrix}{{{P1\_ X}(m)} = \left\{ \begin{matrix}0 & {{m = 0},1,\ldots \mspace{14mu},158} \\{{SC}\left( \frac{m - 159}{2} \right)} & {{m = 159},161,{{\ldots \mspace{14mu} 159} + {176*2}}} \\{{FC}\left( \frac{m - 159 - 1}{2} \right)} & {{{m = 160},162,{160 + {176*2}}}\;} \\{{FC}\left( \frac{m - 159}{2} \right)} & \begin{matrix}{m = {161 + {176*{{2,163} +}}}} \\{{176*{2,159}} + {352*2}}\end{matrix} \\{{SC}\left( \frac{m - 159 - 1}{2} \right)} & \begin{matrix}{m = {162 + {176*}}} \\{{{2,164} + {176*2}},{{\ldots \mspace{14mu} 160} + {352*2}}}\end{matrix} \\0 & {{m = 865},{\ldots \mspace{14mu} 1023}}\end{matrix} \right.} & \left( {{Formula}\mspace{14mu} 32} \right)\end{matrix}$

With regard to a united symbol formed by assembling two time-domainsymbols with three-segment structure, the step of generating afrequency-domain OFDM symbol corresponding to two time-domain main bodysignals thereof contains: any of the above-mentioned signalling sequencegeneration steps or fixed sequence generation steps or any of the firstpredefined interlaced arrangement rule or the second predefinedinterlaced arrangement rule. Additionally, the structure of thefrequency-domain OFDM symbol corresponding to the two time-domainsymbols with a three-segment structure can also satisfy at least any oneof the following three predefined association rules:

The first predefined association rule: two time-domain OFDM symbolsrespectively adopt the same set of signalling sequences. For example, if10 bits are transmitted by a single symbol according to the abovestatement, the total transmission capacity is 20 bits in total.

The second predefined association rule: the fixed sequence of the secondtime-domain OFDM symbol and the fixed sequence of the first time-domainOFDM symbol keep the same.

The third predefined association rule: the positions of the validsubcarriers containing a fixed sequence and a signalling sequence in thesecond time-domain OFDM symbol are the integral left-wise or right-wiseshift of the positions of the valid subcarriers in the first time-domainOFDM symbol, and the shift value is generally controlled to be in therange of 0-5.

FIG. 11 and FIG. 12 are respectively schematic diagrams of integralshift of frequency-domain symbols corresponding to two time-domain mainbody signals according to the third predefined association rule with afirst shift value and a second shift value. The first shift value inFIG. 11 is 1, and the second shift value in FIG. 12 is 2.

In the united time-domain symbol containing a plurality of three-segmentstructures, for example two three-segment structures, the preferredembodiment of generating a frequency-domain symbol for a time-domainmain body signal A1 in the first three-segment structure and atime-domain main body signal A2 in the second three-segment structure isas follows:

A frequency-domain symbol corresponding to a time-domain main bodysignal A1 of a first time-domain symbol in a united preamble symbol isidentical to the frequency-domain symbol in the common preamble symbolgenerated according to the second predefined interlaced arrangement ruleintroduced above, the FC and SC sequence and the frequency domainposition arrangement and zero carrier positions are exactly the same.

A frequency-domain symbol corresponding to a time-domain main bodysignal A2 of a second time-domain symbol in a united preamble symbol isidentical with the FC and SC sequence of the common preamble symbolgenerated according to the second predefined interlaced arrangement ruleintroduced above, and the positions of the valid subcarriers of thefrequency-domain symbol corresponding to A2 is an integral one-unitleft-wise shift of the frequency-domain symbol corresponding to A1.i.e.,

$\begin{matrix}{{{P2\_ X}(m)} = \left\{ \begin{matrix}0 & {{m = 0},1,\ldots \mspace{14mu},157} \\{{SC}\left( \frac{m - 158}{2} \right)} & {{m = 158},160,{{\ldots \mspace{14mu} 158} + {176*2}}} \\{{FC}\left( \frac{m - 158 - 1}{2} \right)} & {{{m = 159},161,{159 + {176*2}}}\;} \\{{FC}\left( \frac{m - 158}{2} \right)} & \begin{matrix}{m = {160 + {176*2,162} +}} \\{{176*2,158} + {352*2}}\end{matrix} \\{{SC}\left( \frac{m - 158 - 1}{2} \right)} & \begin{matrix}{m = {161 + {176*}}} \\{{{2,163} + {176*2}},{{\ldots \mspace{14mu} 159} + {352*2}}}\end{matrix} \\0 & {{m = 864},{\ldots \mspace{14mu} 1023}}\end{matrix} \right.} & \left( {{Formula}\mspace{14mu} 33} \right)\end{matrix}$

[Frequency-Domain Structure II]

Description is made below to a method for generating a frequency-domainOFDM symbol with the following frequency-domain structure II. Thefrequency-domain structure of the second type of P1_X is elaborated, andis defined as frequency-domain structure II. For frequency-domainstructure II, the frequency-domain symbol generation method comprisesthe following steps:

generating a frequency-domain main body sequence with a predefinedsequence generation rule; and/or

processing the frequency-domain main body sequence with a predefinedprocessing rule to generate a frequency-domain symbol,

wherein the predefined sequence generation rule contains either one or acombination of two of the following:

generating a sequence based on different sequence generation formulas;and/or generating a sequence based on the same sequence generationformula, and further preforming cyclic shift on the generated sequence.

the predefined processing rule contains: according to the predefinedfrequency offset value, performing phase modulation on a pre-generatedsubcarrier which is obtained by processing the frequency-domain mainbody sequence.

FIG. 13 is a schematic diagram of the arrangement of frequency-domainstructure II corresponding to a time-domain symbol in the preamblesymbol of the embodiments of the present invention;

The preamble symbol as previously stated contains at least onetime-domain symbol, and a frequency-domain subcarrier corresponding tothe time-domain symbol is obtained based on a frequency-domain main bodysequence.

The generation of the frequency-domain subcarrier is described throughFIG. 13. The frequency-domain subcarrier contain a predefined sequencegeneration rule for generating the frequency-domain main body sequenceand/or a predefined processing rule for processing the frequency-domainmain body sequence for generating the frequency-domain subcarrier.

For the predefined sequence generation rule, the process of generatingthe frequency-domain main body sequence is relatively flexible. Thepredefined sequence generation rule contains any one or a combination oftwo of the following: generating a sequence based on different sequencegeneration formulas; and/or generating a sequence based on the samesequence generation formula, and further preforming cyclic shift on thegenerated sequence. In this embodiment, the generation process isrealized using a constant amplitude zero auto-correlation sequence(CAZAC sequence); that is to say, the above-mentioned different sequencegeneration formulas are obtained by assigning different root values tothe same CAZAC sequence, and it can also be that the same sequencegeneration formula mentioned above is obtained by assigning the sameroot value to the CAZAC sequence.

The frequency-domain main body sequence is generated based on one ormore CAZAC sequences, and the frequency-domain main body sequence has apredefined sequence length N_(ZC). The predefined sequence length N_(ZC)is not greater than a Fourier transform length N_(FFT) of thetime-domain main body signal.

In general, the step of processing and filling with the frequency-domainmain body sequence comprises: mapping the frequency-domain main bodysequence to positive frequency subcarriers and negative frequencysubcarriers with reference to the predefined sequence length N_(ZC),filling a predefined number of virtual subcarriers and direct-currentsubcarrier at the outer edge of the positive frequency subcarriers andthe negative frequency subcarriers with reference to the Fouriertransform length N_(FFT); and performing cyclic left-wise shift on theresulting subcarriers, so that the zero subcarrier corresponds to thefirst position in inverse Fourier transform.

Herein, an example of generation based on one CAZAC sequence is listed.

First of all, a frequency-domain main body sequence (Zadoff-Chu,sequence ZC) with a length of N_(ZC) is generated, which is one of CAZACsequences.

Assuming that the sequence formula is:

$\begin{matrix}{{a_{q}(n)} = e^{{- j}\; \pi \; q\frac{n{({n + 1})}}{N_{root}}}} & \left( {{Formula}\mspace{14mu} 34} \right)\end{matrix}$

No that N_(ZC) can be equal to or smaller than N_(root), namely, it canbe generated by a complete Zadoff-Chu sequence with some root value inits entirety or by truncating the ZC sequence; then it is selectable tomodulate the ZC sequence with a PN sequence having the same length toobtain a ZC_M sequence; the ZC_M sequence is divided into two parts,i.e. a left half part having a length of

$\frac{N_{ZC} + 1}{2}$

and being mapped to a negative frequency part of subcarriers, and aright half part having a length of

$\frac{N_{ZC} - 1}{2}$

and being mapped to a positive frequency part of subcarriers; N_(ZC) canbe selected as some natural number, and does not exceed the FFT lengthof segment A. Additionally, at the edge of the negative frequency ofsubcarriers,

$\frac{N_{FFT} - N_{ZC} - 1}{2}$

zeros are added, and at the edge of the positive frequency ofsubcarriers,

$\frac{N_{FFT} - N_{ZC} - 1}{2}$

zeros are added, as virtual subcarriers. Therefore, the specificsequence is composed by

$\frac{N_{FFT} - N_{ZC} - 1}{2}$

zeros,

$\frac{N_{ZC} + 1}{2}$

PN-modulated ZC sequences, 1 direct-current subcarrier,

$\frac{N_{ZC} - 1}{2}$

PN-modulated ZC sequences and

$\frac{N_{FFT} - N_{ZC} - 1}{2}$

zeros sequentially; and the number of valid subcarriers is N_(ZC)+1.

To describe the process of generating the frequency-domain main bodysequence particularly, taking the sequence formula

${a_{q}(n)} = e^{{- j}\; \pi \; q\frac{n{({n + 1})}}{N_{root}}}$

as an example, several different root values q can be selected; and forthe sequence generated by each root value q, different cyclic shift canbe performed again to obtain more sequences; either or both of the twomodes are adopted to transmit signalling.

By way of example, if 256 root values q are taken, and 256 sequences areobtain, then 8 bits can be transmitted, which is based on 2̂8=256; and ashift value is set to 1024, each of the 256 sequences can be shifted by0-1023, that is, each sequence realizes the transmission of another 10bits of signalling via 1024 shifts, which is based on 2̂10=1024; thus8+10=18 bits of signalling can be transmitted together.

These signalling is mapped to a bit field, and the transmittedsignalling can be used for indicating frame format parameters of aphysical frame and/or for indicating an emergency broadcast content,where the frame format parameters include: the number of frames, theframe length, the bandwidth of a subsequent signalling symbol, thebandwidth of data area, the FFT size and guard interval length of thesignalling symbol, modulation and coding parameters of the signallingsymbol, etc.

The cyclic shift in the above-mentioned predefined sequence generationrule can be performed before PN sequence modulation of the ZC sequence,and can also be performed after the PN sequence modulation. Inadditional, PN modulation can be performed on the frequency-domain mainbody sequence corresponding to each of the time-domain main body signalsby using the same or different PN sequences.

It is known that a physical frame structure contains a preamble symboland a data area, wherein the preamble symbol contains a physical-layerformat control (PFC) part and a physical-layer content control (PCC)part.

If a time-domain main body signal of a first time-domain symbol in thepreamble symbol correspondingly employs a frequency-domain main bodysequence known in advance, then the frequency-domain main body sequenceand the corresponding frequency offset value will not be used forsignalling transmission, but signalling transmission is performed by thephysical-layer format control (PFC) part in subsequent time-domainsymbols.

The phase of a frequency-domain main body sequence (ZC sequence) used bythe last time-domain OFDM symbol differs from that of a frequency-domainmain body sequence (ZC sequence) used by the first time-domain OFDMsymbol by 180 degrees, which is used for indicating the last time-domainOFDM symbol of the PFC. The ZC sequence used by the first time-domainOFDM symbol in the PFC is generally a root sequence with a predefinedlength and without cyclic shift, and under this length, the ZC sequencehas a set; therefore, in the present invention, a certain sequence inthis set, is used to indicate specific information, e.g. a versionnumber, or to indicate the type or mode of a service transmitted in thedata frame. Additionally, information is transmitted using thecorresponding root value in the first time-domain main body signaland/or using an initial phase of the PN modulation sequence, wherein theinitial phase of the PN modulation sequence also has some signallingcapability, e.g. indicating the version number.

Herein, an example of generating a frequency-domain main body sequenceusing a plurality of CAZAC sequences is listed.

Each CAZAC sequence has a corresponding sub-sequence length L_(M); foreach CAZAC sequence, a sub-sequence with a sub-sequence length L_(M) isgenerated according to the above-mentioned predefined sequencegeneration rule; and a plurality of sub-sequences are assembled into afrequency-domain main body sequence with a predefined sequence lengthN_(ZC).

Specifically, in the generation of frequency-domain valid subcarrier, MCAZAC sequences are included; assuming that the lengths of the M CAZACsequences are respectively L₁, L₂, . . . , L_(M), and satisfy

${{\sum\limits_{i = 1}^{M}\; L_{M}} = N_{ZC}};$

the generation method for each CAZAC sequence is the same as thatmentioned above, with only one step added; the M CAZAC sequences aregenerated and assembled into a sequence with a length N_(ZC); it isselectable to use a PN sequence to modulate the CAZAC sequence to formZC_M; frequency domain interleaving is then performed to form a new ZC_I and then fill the above-mentioned same subcarrier with it; a lefthalf part has a length of

$\frac{N_{ZC} + 1}{2}$

and is mapped to a negative frequency part of subcarriers, and a righthalf part has a length of

$\frac{N_{ZC} - 1}{2}$

and is mapped to a positive frequency part of subcarriers; N_(ZC) can beselected as some natural number, and does not exceed the FFT length ofsegment A. Additionally, at the edge of the negative frequency ofsubcarriers,

$\frac{N_{FFT} - N_{ZC} - 1}{2}$

zeros are added, and at the edge of the positive frequency ofsubcarriers,

$\frac{N_{FFT} - N_{ZC} - 1}{2}$

zeros are added, as virtual subcarriers. Therefore, the specificsequence is composed by

$\frac{N_{FFT} - N_{ZC} - 1}{2}$

zeros,

$\frac{N_{ZC} + 1}{2}$

PN-modulated ZC sequences, 1 direct-current subcarrier,

$\frac{N_{ZC} - 1}{2}$

PN-modulated ZC sequences and

$\frac{N_{FFT} - N_{ZC} - 1}{2}$

zeros sequentially, wherein the step of PN modulation can also beperformed after the frequency domain interleaving.

Other processing and filling steps can also be used to carry outsubcarrier filling, which is not limited herein.

The subcarrier obtained through the processing and filling above iscyclically left-wise shifted; after the interchange between the firsthalf and latter half of frequency spectrum, which is similar to fftshiftoperation in Matlab, i.e. enabling a zero subcarrier to correspond tothe first position of inverse discrete Fourier transform, apre-generated subcarrier of the frequency-domain OFDM with a predefinedlength of N_(FFT) is obtained.

Further, in a frequency-domain subcarrier generation process in thisembodiment, besides preferably adopting the above-mentioned predefinedsequence generation rule, it is also possible to adopt a predefinedprocessing rule of preferably processing the frequency-domain main bodysequence to generate a frequency-domain subcarrier. In the presentinvention, it is not restricted to use any one or a combination of twoof the predefined processing rule and the predefined sequence generationrule to generate a frequency-domain subcarrier.

The predefined processing rule contains: performing phase modulation onthe pre-generated subcarrier according to a frequency offset value S,wherein the pre-generated subcarrier is obtained through theabove-mentioned steps of processing and filling, and performing cyclicleft-wise shift on the frequency-domain main body sequence. In thepredefined processing rule, phase modulation is performed on each validsubcarrier in frequency-domain subcarriers corresponding to the sametime-domain main body signal A using the same frequency offset value S,the offset values S used for the frequency-domain subcarrierscorresponding to different time-domain main body signal A are different.

Particularly, for the predefined processing rule, such as assuming thatthe expression of the subcarrier of an original OFDM symbol is:

a ₀(k) k=0,1,2, . . . N _(FFT)−1,   (Formula 35)

then the expression for phase modulation on each subcarrier according tosome frequency offset value, such as S is as follows:

$\begin{matrix}{{{a_{s}(k)} = {{a_{0}(k)} \cdot e^{j\frac{2\; \pi \; {sk}}{N_{FFT}}}}}{{k = 0},1,2,{{\ldots \mspace{14mu} N_{FFT}} - 1}}} & \left( {{Formula}\mspace{14mu} 36} \right)\end{matrix}$

where the multiplication operation of zero subcarrier does not need tobe actually conducted, operation needs only to be conducted on the validsubcarriers. The frequency offset value s can be selected as an integerin the range of [−(N_(FFT)−1), +(N_(FFT)−1)]; and the frequency offsetvalue corresponding to this time-domain main body signal is determinedaccording to a Fourier transform length N_(FFT) of the time-domain mainbody signal, different values of which can be used for transmittingsignalling.

It should be noted that the above-mentioned implementation of performingphase modulation on each pre-generated subcarrier according to afrequency offset value S can also be realized in the time domain. It isequivalent to: IFFT transform is performed on an originalfrequency-domain OFDM symbol with an un-modulated phase to obtain atime-domain OFDM symbol; cyclic shift can be performed on thetime-domain OFDM symbol to generate a time-domain main body signal A;and signalling is transmitted through different cyclic shift values. Inthe present invention, description is made by performing phasemodulation on each valid subcarrier according to some frequency shiftvalue in the frequency domain; and apparently, equivalent operationmethods thereto in the time domain are also included in the presentinvention.

In summary, in this embodiment, in the process of generating afrequency-domain subcarrier, it is possible to select, based on thefrequency-domain main body sequence, any one or a free combination of atleast two of the above-mentioned predefined sequence generation rule(1a) and predefined sequence generation rule (1b), and the predefinedprocessing rule (2).

For example, signalling is transmitted by means of the preamble symbolgeneration method in the predefined sequence generation rule (1a).

For example, the root value q described in the previous example has 256values, and the cyclic shift value of each root value q is taken to be0-1023; then 8+10=18 bits of signalling can be transmitted.

For another example, signalling is transmitted by means of the preamblesymbol generation method in the predefined sequence generation rule (1a)and the predefined processing rule (2).

The root value q are taken to be 2 values, the length of the time-domainOFDM symbol is 2048, 1024 shift values are taken, and an interval istaken to be 2, such as 0, 2, 4, 6, . . . , 2046, etc., so as to transmit1+10=11 bits of signalling.

For another example, only the preamble symbol generation method in thepredefined processing rule (2) is used.

The root value q is fixed, and phase modulation is performed on thefrequency-domain subcarrier according to different frequency offsetvalues S, for example, the aforementioned N_(FFT) is 2048, and the svalue for

${a_{s}(k)} = {{a_{0}(k)} \cdot e^{j\frac{2\; \pi \; {sk}}{N_{FFT}}}}$k = 0, 1, 2, …  N_(FFT) − 1

is 0, 8, 16, . . . , 2032, etc.; this is equivalent to the case ofperforming cyclic shifts with 256 different shift values on thetime-domain OFDM symbol which is obtained after performing IFFT on aphase unmodulated frequency-domain OFDM symbol, and taking 8 as aninterval, such as 0, 8, 16, . . . , 2032, etc., so as to transmit 8 bitsof signalling. Here, the present invention, the shift direction of thecyclic shift is not restricted; when s is a positive number, itcorresponds to a cyclic left-wise shift in the time domain, e.g. whenits value is 8, it corresponds to 8 units of cyclic left-wise shift inthe time domain; and when s is a negative number, it correspond to acyclic right-wise shift in the time domain, e.g. when its value is −8,it corresponds to 8 units of cyclic right-wise shift in the time domain.

Additionally, in the above-mentioned frequency-domain symbol generationmethod, the method for transmitting signalling using a frequency-domainmodulation frequency offset value, i.e. a time-domain shift value, isnot restricted; both directly transmitting signalling using the absoluteshift of a current symbol and transmitting signalling using a differencebetween shift values of the previous and latter symbols are included;and with respect to the signalling parsing for both methods, one of themcan be obviously derived from the other one. At the same time, acorresponding relationship between signalling and a shift value is norestricted either; for a transmitting end, it can be set freely, and fora receiving end, it can be inferred backwards according to a determinedrule. An example of transmitting signalling using the absolute value ofthe shift for each symbol is as follows: for example, there are 4symbols in all, wherein the first symbol is not for signallingtransmission, and the signalling values to be transmitted by the secondto the fourth symbols are respectively S1, S2 and S3. Assuming that avalue which is 4 times of the signalling is taken as a correspondingshift value, then the shift value of the second symbol is 4S1, the shiftvalue of the second symbol is 4S2, and the shift value of the thirdsymbol is 4S3. An example of transmitting signalling using thedifference between shift values of the before and after symbols is asfollows: for example, there are 4 PFC symbols in all, wherein the firstsymbol is not for signalling transmission, and the signalling values tobe transmitted by the second to the fourth symbols are respectively S1,S2 and S3. Assuming that a value which is 4 times of the signalling istaken as a corresponding shift value, then the shift value of the secondsymbol is 4S1, the shift value of the second symbol is 4(S1+S2), and theshift value of the third symbol is 4(S1+S2+S3).

Receiving Method

This embodiment also provides a preamble symbol receiving method. Thepreamble symbol receiving method is applicable to a preamble symbolgenerated by a transmitting end with a predefined generation rule.

In the predefined generation rule, the generated preamble symbolcontains all the technological factors involved in the firstthree-segment structure and/or the second three-segment structuredescribed above from the view of time domain in this embodiment, and/orcontains all the technological factors involved in for example thefrequency-domain structure I and the frequency-domain structure IIdescribed above from the view of frequency domain in this embodiment,which will not be described herein anymore. Therefore, in brief, theapplicable predefined generation rule contains the above-mentionedpreamble symbol generation method described from the view of time domainand the frequency-domain symbol generation method described from theview of frequency domain without loss of generality.

A preamble symbol generated according to the predefined generation rulerespectively has the above-mentioned time-domain three-segmentstructure, has the above-mentioned corresponding frequency-domainstructure I, and has the above-mentioned corresponding frequency-domainstructure II. Description is made below with regard to the preamblesymbol receiving method.

[The Preamble Symbol Satisfies the Condition of having Time-DomainSymbols with the Above-Mentioned Three-Segment Structure]

This embodiment also provides a preamble symbol receiving method,comprising the following steps:

step S11: processing a received signal;

step S12: judging whether the processed signal contains theabove-mentioned preamble symbol with three-segment structure desired tobe received; and

step S13: in the case where a judgement result above is yes, determiningthe position of the preamble symbol and resolving signalling informationcarried by the preamble symbol,

wherein the received preamble symbol comprises: a preamble symbolgenerated by a transmitting end through a free combination of any numberof first three-segment structures and/or second three-segment structuresaccording to a predefined generation rule, which contains at least onetime-domain symbol.

The first three-segment structure as stated above contains: atime-domain main body signal, a prefix generated based on the entiretyor a portion of the time-domain main body signal, and a postfixgenerated based on the entirety or a portion of a partial time-domainmain body signal.

The second three-segment structure as stated above contains: thetime-domain main body signal, the prefix generated based on the entiretyor a portion of the time-domain main body signal, and a hyper prefixgenerated based on the entirety or a portion of a partial time-domainmain body signal.

As stated in step S11, the received physical frame signal is processedto obtain a baseband signal. A signal received by the receiving end isgenerally an analogue signal, thus analog-to-digital conversion shouldbe performed thereon to obtain a digital signal at first, thenprocessing such as filtering, down-sampling or the like is performed toobtain the baseband signal. It should be noted that if the receiving endreceives an intermediate frequency signal, after performinganalog-to-digital conversion processing thereon, frequency spectrumshift is also required, then processing such as filtering, down-samplingor the like is performed to obtain the baseband signal

As stated in step S12: whether the baseband signal contains theabove-mentioned preamble symbol with a three-segment structure desiredto be received is judged.

Specifically, first of all, the receiving end will judge whether thereceived baseband signal contains the preamble symbol desired to bereceived, i.e. whether the received signal meets a receiving standard;for example, if the receiving end needs to receive data of DVB_T2standard, whether the received signal contains a preamble symbol of theDVB_T2 standard should be judged; in the same way, here, whether thereceived signal contains a time-domain symbol with a C−A−B and/or B−C−Athree-segment structure needs to be judged.

The steps of judging whether the processed received signal contains thepreamble symbol desired to be received, determining the position of thepreamble symbol and solving signalling information carried by thepreamble symbol, i.e. the above-mentioned steps S12 and S13, contain atleast any one of the following steps: initial timing synchronization, anintegral multiple of frequency offset estimation, fine timingsynchronization, channel estimation, decoding analysis and fractionalfrequency offset estimation.

Any one or a free combination of any at least two methods can be used toconduct reliability judgement, i.e. judging if the processed signalcontains the preamble symbol desired to be received: an initial timingsynchronization method, an integer frequency offset estimation method, afine timing synchronization method, a channel estimation method, adecoding result analysis method and a fractional frequency offsetestimation method.

Step S12 contains S12-1 the initial timing synchronization method forpreliminarily determining the position of the preamble symbol in thephysical frame, and also contains S12-2 judging whether the basebandsignal contains the above-mentioned preamble symbol with a three-segmentstructure desired to be received, based on a result of the initialtiming synchronization method. With regard to the initial timingsynchronization method, the initial timing synchronization can becompleted by using any one or a combination of both of the initialtiming synchronization method ({circle around (1)}) and the initialtiming synchronization method ({circle around (2)}) below.

[Initial Timing Synchronization Method ({circle around (1)})]

Initial timing synchronization method ({circle around (1)}) isspecifically introduced below. Initial timing synchronization method({circle around (1)}) contains the following steps:

performing necessary inverse processing on the processed signal byutilizing a processing relationship between any two segments in a firstpredefined three-segment time-domain structure and/or a secondpredefined three-segment time-domain structure, and performing delayedmoving autocorrelation to acquire basic accumulation correlation values;

when the signal comprises at least two time-domain symbols with athree-segment structure, grouping the basic accumulation correlationvalues obtained according to delayed moving auto-correlation accordingto different delay lengths, and performing another delay relationshipmatch and/or phase adjustment during at least one symbol period betweenat least two time-domain symbols with specific assembling relationshipin each group, and then carrying out a mathematical calculation toobtain several final accumulation correlation values with a certaindelay length; and when there is only one time-domain symbol with athree-segment structure, the final accumulation correlation value is thebasic accumulation correlation value; and

after performing delay relationship match and/or a specific predefinedmathematical calculation based on at least one of the final accumulationcorrelation values, using the result of the calculation for initialtiming synchronization;

Particularly, performing delay relationship match and/or phaseadjustment between one, or two or more symbols includes: performingdelay relationship match and/or phase adjustment on one symbol, which isequivalent to that no operation is conducted, and performing delayrelationship match and/or phase adjustment between two or more symbols,which comprises a practical operation.

According to processing relationships and/or modulation relationshipsbetween the third part C (corresponding to the prefix), the first part A(corresponding to the time-domain main body signal) and the second partB (corresponding to the postfix or the hyper prefix) in thethree-segment structure desired to be received, necessary inverseprocessing and/or signal demodulation, and then delayed movingauto-correlation are performed on the baseband signal, to obtain any oneor any at least two of three accumulation correlation values between thethird part C and the first part A, between the first part A and thesecond part B, and between the third par C and the second part B in theobtained three-segment structure, i.e. U_(ca)′(n) U_(cb)′(n) andU_(ab)′(n). A correlation value for detection is obtained based on atleast one of the accumulation correlation value.

For example, assuming that the three-segment structure is C−A−Bstructure,

based on the delay relationship between the third part C and the firstpart A, delayed moving auto-correlation is performed on the receivedsignal, for which the delayed correlation expression U_(ca)(n) and thedelayed accumulation correlation value U_(ca)′(n) are as follows:

$\begin{matrix}{{{U_{ca}(n)} = {{r(n)}{r^{*}\left( {n - N_{A}} \right)}}}{{U_{ca}^{\prime}(n)} = {\frac{1}{{Len}_{C}}{\sum\limits_{k = 0}^{{Len}_{C} - 1}\; {U_{ca}\left( {n - k} \right)}}}}} & \left( {{{Formulas}\mspace{14mu} 37\text{-}1};\; {{and}\mspace{14mu} 37\text{-}2}} \right)\end{matrix}$

Energy normalization can optionally be conducted on U_(ca)′(n).

That is,

$\begin{matrix}{{U_{ca}^{\prime}(n)} = \frac{U_{ca}^{\prime}(n)}{0.5\frac{1}{{Len}_{C}}{\sum\limits_{k = 0}^{{Len}_{C} - 1}\left( {{{r\left( {n - k} \right)}}^{2} + {{r\left( {n - k - N_{A}} \right)}}^{2}} \right)}}} & \left( {{Formula}\mspace{14mu} 38} \right)\end{matrix}$

based on the processing relationship between the second part B and thethird part C and a modulation frequency offset value, delayed movingauto-correlation and demodulation are performed on the received signal,for which the delayed correlation expression U_(cb)(n) and the delayedaccumulation correlation value U_(cb)′(n) are as follows:

$\begin{matrix}{{{U_{cb}(n)} = {{r(n)}{r^{*}\left( {n - N_{A} - N_{A} + {N\; 1}} \right)}e^{{- {jnf}_{SH}}T}}}\mspace{79mu} {{U_{cb}^{\prime}(n)} = {\frac{1}{corr\_ len}{\sum\limits_{k = 0}^{{{corr}\_ {len}} - 1}\; {U_{cb}\left( {n - k} \right)}}}}} & \left( {{{Formula}\mspace{14mu} 39\text{-}1};\; {39\text{-}2}} \right)\end{matrix}$

Also, energy normalization can be conducted on U_(cb)′(n).

Based on the processing relationship between the second part B and thefirst part A and a modulation frequency offset value, delayed movingcorrelation is performed on the received signal, for which the delayedcorrelation expression U_(ab)(n) and the delayed accumulationcorrelation value U_(ab)′(n) are as follows:

$\begin{matrix}{{{U_{ab}(n)} = {{r(n)}{r^{*}\left( {n - N_{A} - N_{A} + {N\; 1}} \right)}e^{{- {jnf}_{SH}}T}}}\mspace{79mu} {{U_{ab}^{\prime}(n)} = {\frac{1}{corr\_ len}{\sum\limits_{k = 0}^{{corr\_ len} - 1}\; {U_{ab}\left( {n - k} \right)}}}}} & \left( {{{Formula}\mspace{14mu} 40\text{-}1};\; {40\text{-}2}} \right)\end{matrix}$

Also, energy normalization can be conducted on U_(ab)′(n).

corr_len can not only be taken as 1/f_(SH)T to avoid continuous waveinterference, but also can be taken as Len_(B) to obtain a sharp peak.

Performing required delay match and mathematical calculation by usingthe delayed accumulation correlation values U_(ca)′(n), U_(cb)′(n), andU_(ab)′(n); the mathematical calculation contains multiplication oraddition, using such as U_(cb)′(n)·U_(ab)′*(n) or

U_(ca)′(n−N_(A)+N1)·U_(cb)′(n)·U_(ab)′*(n) to obtain an calculationvalue, i.e. the correlation value 1 to be detected.

FIG. 14 is a logic diagram of obtaining correlation result to bedetected corresponding to a three-segment structure CAB in theembodiments of the present invention. C, A and B in the Figurerespectively indicate the length of segment C, segment A and segment Bof a signal, and a moving average filter can be a power normalizationfilter, where A is N_(A), B is Len_(B), and C is Len_(C).

For example, assuming that the three-segment structure is B−C−Astructure,

based on the delay relationship between the third part C and the firstpart A, delayed moving auto-correlation is performed on the receivedsignal, for which the delayed correlation expression U_(ca)(n) and thedelayed accumulation correlation value U_(ca)′(n) are as follows:

$\begin{matrix}{{{U_{ca}(n)} = {{r(n)}{r^{*}\left( {n - N_{A}} \right)}}}{{U_{ca}^{\prime}(n)} = {\frac{1}{{Len}_{C}}{\sum\limits_{k = 0}^{{Len}_{C} - 1}\; {U_{ca}\left( {n - k} \right)}}}}} & \left( {{{Formula}\mspace{14mu} 41\text{-}1};\; {41\text{-}2}} \right)\end{matrix}$

Energy normalization can be conducted on U_(ca)′(n).

That is,

$\begin{matrix}{{U_{ca}^{\prime}(n)} = \frac{U_{ca}^{\prime}(n)}{0.5\frac{1}{{Len}_{C}}{\sum\limits_{k = 0}^{{Len}_{C} - 1}\left( {{{r\left( {n - k} \right)}}^{2} + {{r\left( {n - k - N_{A}} \right)}}^{2}} \right)}}} & \left( {{Formula}\mspace{14mu} 42} \right)\end{matrix}$

Based on the processing relationship between the second part B segmentand the third part C segment and a modulation frequency offset value,delayed moving auto-correlation is performed on the received signal, andthe frequency offset is demodulated; note that the delayed correlationexpression U_(cb)(n) and the delayed accumulation correlation valueU_(cb)′(n) are as follows:

$\begin{matrix}{{{U_{cb}(n)} = {{r(n)}{r^{*}\left( {n - N_{A} - N_{A} + {N\; 1}} \right)}e^{{- {jnf}_{SH}}T}}}\mspace{79mu} {{U_{cb}^{\prime}(n)} = {\frac{1}{corr\_ len}{\sum\limits_{k = 0}^{{corr\_ len} - 1}\; {U_{cb}\left( {n - k} \right)}}}}} & \left( {{{Formula}\mspace{14mu} 43\text{-}1};\; {43\text{-}2}} \right)\end{matrix}$

Also, energy normalization can be conducted on U_(cb)′(n).

Based on the processing relationship between the second part B segmentand the first part A segment and a modulation frequency offset value,delayed moving correlation is performed on the received signal, forwhich the delayed correlation expression U_(ab)(n) and the delayedaccumulation correlation value U_(ab)′(n) are as follows:

$\begin{matrix}{{{U_{ab}(n)} = {{r(n)}{r^{*}\left( {n - N_{A} - N_{A} + {N\; 1}} \right)}e^{{- {jnf}_{SH}}T}}}\mspace{79mu} {{U_{ab}^{\prime}(n)} = {\frac{1}{corr\_ len}{\sum\limits_{k = 0}^{{corr\_ len} - 1}\; {U_{ab}\left( {n - k} \right)}}}}} & \left( {{{Formula}\mspace{14mu} 44\text{-}1};\; {44\text{-}2}} \right)\end{matrix}$

Also, energy normalization can be conducted on U_(ab)′(n).

corr_len can be valued 1/f_(SH)T to avoid continuous wave interference,or can be valued Len_(B) to enable the peak to be sharp.

Performing required delay match and mathematical calculation by usingthe delayed accumulation correlation values U_(ca)′(n), U_(cb)′(n), andU_(ab)′(n); the mathematical calculation contains addition ormultiplication, using such as U_(cb)′*(n−N_(A))·U_(ab)′(n) or

U_(ca)′(n)·U_(cb)′*(n−N_(A))·U_(ab)′(n) to obtain an calculation value,i.e. the correlation value 1 to be detected.

FIG. 15 is a logic diagram of obtaining correlation result to bedetected corresponding to a three-segment structure BCA in theembodiments of the present invention.

Only one set of receiving resources are needed for the same portion inFIG. 14 and FIG. 15, they are shown in a separated mode for the sake ofclarity. C, A and B in the Figure respectively indicate the length ofsegment C, segment A and segment B of a signal, and a moving averagefilter can be a power normalization filter, where A is N_(A), B isLen_(B), and C is Len_(C).

A correlation value for preliminary timing synchronization are formedbased on the correlation result 1 to be detected and/or the correlationresult 2 to be detected.

Further, when both the following two situations (a) and (b) arecontained in preamble symbol transmission,

(a) the time-domain main body signal contains known information;

(b) and it is detected that the time-domain symbol has the C−A−Bthree-segment structure,

the initial timing synchronization can be completed by means of any oneor a combination of both of the above-mentioned initial timingsynchronization method ({circle around (1)}) and the initial timingsynchronization method ({circle around (2)}) below. When the twosynchronization methods are completed, a first preliminarysynchronization calculation value obtained via the initial timingsynchronization method ({circle around (1)}) and a second preliminarysynchronization calculation value obtained via the initial timingsynchronization method ({circle around (2)}) are weighted, and initialtiming synchronization is completed based on the weighted arithmeticvalue.

[Initial Timing Synchronization Method ({circle around (2)})]

Initial timing synchronization method ({circle around (2)}) isspecifically introduced in the following.

When any C−A−B and/or B−C−A main body signal A contains knowninformation, such as a fixed subcarrier, or such as when a preamblesymbol contains several time-domain symbols with a C−A−B and/or a B−C−Athree-segment structure, and a main body signal A of some of thetime-domain symbols is a known signal, that is, when any time-domainmain body signal in the preamble symbol contains a known signal, theinitial timing synchronization method ({circle around (2)}) comprises:performing differential operation on the time-domain main body signal Ain accordance with predefined N differential values, and performingdifferential operation on a time-domain signal corresponding to knowninformation as well, then correlating the two to obtain N sets ofdifferential correlated results corresponding to the N differentialvalues on a one-to-one basis, and performing initial synchronizationbased on the N sets of differential correlated results to obtainprocessed values which are used for preliminarily determining theposition of the preamble symbol, where N≧1.

The particular process of differential correlation in the initial timingsynchronization method ({circle around (2)}) is described below; and asingle set of differential correlation process is introduced at first.

A differential value is determined; differential operation is conductedon received baseband data according to the differential value;differential operation is also performed on a local time-domain sequencecorresponding to known information according to the differential value;and then results of the two differential operation are correlated, toobtain a differential correlation result corresponding to thedifferential value. The calculation process for the single set ofdifferential correlation result is the same with the prior art. Assumingthat the differential value is D, and the received baseband data r_(n);and the description for each particular formula is as follows:

First of all, differential operation is conducted on the receivedbaseband data according to the differential value.

z _(m) ^((D)) =r _(m) r* _(m−D)   (Formula 45)

After the differential operation, phase rotation brought about bycarrier frequency offset has become a fixed carrier phase e^(j2πDΔf),where Δf indicates the carrier frequency offset.

At the same time, differential operation is also performed on atime-domain sequence (such as, obtaining the corresponding time-domainsequence by filling fixed subcarriers according to correspondingpositions, and adding zero at the rest of the positions and performingIFFT calculation).

c _(n) ^((D)) =s _(n) s* _(n−D) n=D, . . . , L−1   (Formula 46)

The received data after the differential operation and the localdifferential sequence are correlated, to obtain

$\begin{matrix}{R_{{dc},m}^{(D)} = {\sum\limits_{n = D}^{L - D}\; {z_{n + m}^{(D)}\left\lbrack c_{n}^{(D)} \right\rbrack}^{*}}} & \left( {{Formula}\mspace{14mu} 47} \right)\end{matrix}$

In the case where a system has neither multipath nor noise,

$\begin{matrix}{R_{{dc},m}^{(D)} = {{\sum\limits_{n = D}^{L - D}\; {z_{n + m}^{(D)}\left\lbrack c_{n}^{(D)} \right\rbrack}^{*}} = {e^{j\; 2\; {\pi D}\; \Delta \; f}{\sum\limits_{n = D}^{L - D}{c_{n + m}^{(D)}\left\lbrack c_{n}^{(D)} \right\rbrack}^{*}}}}} & \left( {{Formula}\mspace{14mu} 48} \right)\end{matrix}$

R_(dc,m) ^((D)) can well provide a correlation peak, and the peak is notaffected by the carrier offset. A frame synchronization/timingsynchronization position is obtained using the following formula

$\begin{matrix}{{\hat{n}}_{0} = {\underset{m}{\arg \; \max}\left\{ {R_{{dc},m}^{(D)}} \right\}}} & \left( {{Formula}\mspace{14mu} 49} \right)\end{matrix}$

It can be seen from the above-mentioned process of single set ofdifferential correlation operation that a differential correlationalgorithm can resist the influence from any large carrier frequencyoffset; however, since differential operation is performed on a receivedsequence at first, signal noise is enhanced, and with a lowsignal-to-noise ratio, the noise enhancement is very serious, leading tosignificant deterioration of the signal-to-noise ratio.

In order to avoid the aforementioned problem, not only a single set ofdifferential value is used for correlation calculation, a plurality ofsets of differential correlation operations can be implemented, forexample, taking the value of N to be 64 to implement 64 sets ofdifferential correlation, thus obtaining R_(dc(0),m) ^((D(0))),R_(dc,(1),m) ^((D(1))), . . . , R_(dc(N−1),m) ^((D(N−1))). D(0), D(1), .. . , D(N−1) are the N different differential values selected.

Specific mathematical calculation is performed on N results, to obtain afinal correlation result.

In this embodiment, with respect to a plurality of sets of differentialcorrelation operations (64 sets), a differential value can be selectedby either of the two predefined differential selection rule based on theperformance requirement of a transmission system:

(1) a first predefined differential selection rule: the differentialvalue D(i) is arbitrarily selected to be N different values andsatisfies D(i)<L, where L is the length of a local time-domain sequencecorresponding to the known information.

(2) a second predefined differential selection rule: the differentialvalue D(i) is N different values in arithmetic progression and satisfiesD(i)<L, i.e D(i+1)−D(i)=K, and K is a constant integer satisfying

${K < \frac{L}{N}},$

where L is the length of a local time-domain sequence corresponding tothe known information.

Predefined processing calculation are performed on the N (64) results toobtain a final correlation result, there are two preferred embodimentsfor the predefined processing calculation here, and elaboration will beprovided respectively.

First predefined processing calculation:

the differential value D(i) can be arbitrarily selected to be Ndifferent values and satisfies D(i)<L. Due to the arbitrarily selecteddifferential value D(i), the phase e^(j2πD(i)Δf) i=0, . . . , N−1 aftereach set of differential correlation is different from one another, andcan not be directly added as vectors, weighted addition or average canbe only conducted on absolute values. Predefined processing calculationare performed on N different differential correlation results throughthe following formula, to obtain a final differential result. Theformula below is an example of obtaining a final differential result byabsolute value addition.

$\begin{matrix}{{R_{{dc},m} = {\sum\limits_{i = 0}^{N - 1}\; {{abs}\left( R_{{{dc}{(i)}},m}^{({D{(i)}})} \right)}}}{{i = 0},{{\ldots \mspace{14mu} N} - 1}}} & \left( {{Formula}\mspace{14mu} 50} \right)\end{matrix}$

Second predefined processing calculation:

the differential value D(i) can be arbitrarily selected to be Ndifferent values and satisfies D(i)<L, and satisfies that D(i) is aarithmetic progression, i.e. D(i+1)−D(i)=K; and K is a constant integersatisfying

$K < {\frac{L}{N}.}$

differential values are selected according to such rules; afterobtaining a differential correlation value such as R_(dc(0),m)^((D(0))), R_(dc(1),m) ^((D(1))), . . . , R_(dc(N−1),m) ^((D(N−1))),conjugate multiplication are conducted on adjacent two sets ofdifferential correlation values, to obtain N−1 values after theconjugate multiplication through the following formula.

RM _(i,m) =R _(dc(i),m) ^((D(i)))·(R _(dc(i+1),m) ^((D(i+1))))* i=0,1,2,. . . , N−2   (Formula 51)

Originally different phases e^(j2πD(i)Δf) for each set are changed intothe same phase e^(j2πKΔf) by means of the conjugate multiplication;therefore, weighted vector addition or average can be conducted on theobtained N−1 sets of RM_(i,m) to obtain the final differential result,thus obtaining better performance than the first predefined processingcalculation. The formula below is an example of obtaining a finaldifferential result by vector addition.

$\begin{matrix}{{R_{{dc},m} = {\sum\limits_{i = 0}^{N - 2}\; {RM}_{i,m}}}{{i = 0},{{\ldots \mspace{14mu} N} - 1}}} & \left( {{Formula}\mspace{14mu} 52} \right)\end{matrix}$

It should be noted that, when the differential value D(i) is obtainedusing the above-mentioned second predefined differential selection rule,a final correlation result can not only be obtained by conductingweighted vector addition or average on values after conjugatemultiplication according to the second predefined processingcalculation, the final correlation result but also can be obtained bydirectly conducting weighted absolute value addition or average on atleast two differential correlation result according to theabove-mentioned first predefined processing calculation.

A correlation value for initial timing synchronization is obtained usingR_(dc,m).

Regardless of whether the initial timing synchronization method ({circlearound (1)}) or the initial timing synchronization method ({circlearound (2)}), assuming that a received signal contains a desiredpreamble symbol, the position of the maximum value of the correlationvalue for initial timing synchronization located in a certain range canbe used to preliminarily determine the position of the preamble symbolin the physical frame. A value corresponding to this value is used tofurther judge whether the received signal contains the desired preamblesymbol, or the position is used to conduct subsequent operations, suchas an integral frequency offset estimation and/or decoding, so as tofurther judge whether the received signal contains the desired preamblesymbol.

Based on a result of the above-mentioned initial timing synchronization,whether the processed signal, i.e. the baseband signal, contains theabove-mentioned preamble symbol with a three-segment structure desiredto be received is judged. It particularly comprises: making detectionbased on a result of initial timing synchronization, if the detectedresult satisfies a pre-set condition, then it is determined that thebaseband signal contains the preamble symbol containing thethree-segment structure and desired to be received. Further,satisfaction of the pre-set condition here can not only refer to thefact that a result of initial timing synchronization satisfies a pre-setcondition, but also can refer to the fact that when whether thecondition is satisfied cannot be determined enough according to theresult of initial timing synchronization itself, whether the conditionis satisfied is further determined according to subsequent other steps,such as an integer frequency offset estimation and/or decoding result.

Assuming that the judgement is made directly according to the result ofinitial timing synchronization, the judgement can be made based onwhether a pre-set condition is satisfied; the pre-set condition containsmaking a judgement by performing specific calculation on the result ofinitial timing synchronization, and then judging whether the maximumvalue of an calculation result exceeds a threshold.

Specifically, in the particular implementation of the above-mentionedinitial timing synchronization method ({circle around (1)}), two sets ofdelayed accumulation correlation values corresponding to twothree-segment structures can be obtained according to a predefinedacquisition rule and/or a predefined processing rule between part C,part A and part B of the first three-segment structure and the secondthree-segment structure, and each set include 3 values; two sets ofcorrelation results to be detected are generated using at least one ofthe three delayed accumulation correlation values in each of the 2 sets;thus the resultsare detected, and whether the preamble symbol contains athree-segment structure, and which three-segment structure is containedare judged.

For example, if the first set of correlation results to be detectedsatisfy the pre-set condition, then it is determined that the basebandsignal contains a preamble symbol with the first three-segmentstructure; if the second set of correlation results to be detectedsatisfy the pre-condition, then it is determined that the basebandsignal contains a preamble symbol with the second three-segmentstructure; and the two sets both satisfy the pre-set condition, then itindicates that the preamble symbol contains the two three-segmentstructures at the same time.

When the transmitting end chooses the second part at different startpoints in the time-domain main body signal to transmit signalling, theinitial timing synchronization is used for parsing emergency broadcastthrough any one or a free combination of any two of follows: differentlytransmitting emergency broadcast and common broadcast by utilizingdifferent delay relationships between the same content in the third partand the second part, and different delay relationships between the samecontent in the first part and second part, so as to transmit emergencybroadcast and common broadcast differentially.

By way of example, the receiving end will implement step S12-1 containedin step S12 in a plurality of branches: the initial timingsynchronization method for preliminarily determining the position of thepreamble symbol in the physical frame, and then based on a plurality ofcorrelation results to be detected, judging whether a preamble symboldesired to be received exists, and parsing transmitted time-domainsignalling.

For example, when B is obtained by truncating the preamble symbol fromdifferent start point positions N1 in A, and the start point positionscan be used for transmitting Q bit(s) of signalling, the delayed movingcorrelation for some value N1 above is defined as a branch. Each branchcontains the above-mentioned 3 delayed accumulation correlation values.The receiving end implements the above-mentioned delayed movingauto-correlation branch with 2^(Q) different N1 values, and then judgeswhether the desired preamble symbol exists according to the absolutevalue of 2^(Q) U₂′(n)·U₃′*(n) orU_(ca)′(n−N_(A)+N1)·U_(cb)′(n)·U_(ab)′*(n).

If neither of the absolute values exceeds a threshold, then it indicatesthat the baseband signal does not contain a signal desired to bereceived. Such as, N1 is valued 504 or 520 to transmit 1 bit ofemergency alarm or broadcast system identifier, wherein N1=520 indicatesa normal preamble symbol, and N1=504 indicates an emergency alarm orbroadcast system; then step S21-1 is carried out in 2 branches. Forexample, for a branch in which an emergency alarm broadcast flag is 0,i.e. N1=520, the following are adopted:

performing moving auto-correlation on the received signal which isdelayed by 1024 sampling points with the received signal;

performing moving auto-correlation on the received signal which isdelayed by 1528 sampling points with the received signal of which afrequency offset is demodulated;

performing moving auto-correlation on the received signal which isdelayed by 504 sampling points with the received signal of which afrequency offset is demodulated; and

For example, for a branch in which an emergency alarm broadcast flag is0, i.e. N1=520, the following are adopted:

performing moving auto-correlation on the received signal which isdelayed by 1024 sampling points with the received signal of which afrequency offset is demodulated;

performing moving auto-correlation on the received signal which isdelayed by 1544 sampling points with the received signal of which afrequency offset is demodulated;

performing moving auto-correlation on the received signal which isdelayed by 520 sampling points with the received signal of which afrequency offset is demodulated.

When a threshold is taken as a pre-set condition to judge whether thereceived signal contains the preamble symbol desired to be received,

if the maximum value of the correlation value to be detected of a branchfor with N1=520 exceeds the threshold, it indicates that the basebandsignal is a desired signal, and a preamble symbol appears EAS_flag=0; onthe contrary, if the maximum value of the correlation value to bedetected while N1=504 exceeds the threshold, it indicates thatEAS_flag=1; and if neither of the two sets exceeds the threshold, itindicates that the baseband signal is not a desired signal.

When the preamble symbol utilizes only one of the first three-segmentstructure and the second three-segment structure to identifynon-emergency broadcast, the other one is used to identify emergencybroadcast; and parsing is conducted through the following.

The above-mentioned step S12-1 for two branches corresponding to the twothree-segment structures can be obtained in step S12-1 according to thepredefined acquisition rule and/or the predefined processing rulebetween part C, part A and part B of the first three-segment structureand the second three-segment structure, and each branch includes 3values; and step S12-2 contains detecting a correlation value to bedetected of each of the two branches. If a detection result for a firstbranch satisfies a pre-set condition, then it is determined that thebaseband signal contains the first three-segment structure desired to bereceived, and it indicates that EAS_flag=0; if a detection result for asecond branch satisfies a pre-set condition, then it is determined thatthe baseband signal contains the second three-segment structure desiredto be received, and it indicates that EAS_flag=1; and if it is the casewhere the two branches both satisfy the condition, another judgementshould be made, for example, emergency broadcast can be judged accordingto the obviousness of two peak-to-noise ratios.

Further, after the initial timing synchronization is preliminarilycompleted, initial timing synchronization results from method ({circlearound (1)}) and/or method ({circle around (2)}) can also be used forfractional frequency offset estimation.

When a preliminary timing synchronization method ({circle around (1)})is used, a second fractional frequency offset value can be calculated bytaking the angle of the maximum value in U_(ca)′; after conductingconjugate multiplication on U_(cb)′(n) and U_(ab)′(n) (corresponding toa C−A−B structure) or conducting conjugate multiplication on U_(ab)′(n)and U_(cb)′(n−N_(A)) (corresponding to a B−C−A structure), a thirdfractional frequency offset value can be calculated by taking an anglecorresponding to the maximum value. As shown in the schematic portion inFIG. 14 and FIG. 15 above, an angle in a logical calculation block isused for obtaining the fractional frequency offset, and fractionalfrequency offset estimation can be conducted using any one or two of thesecond fractional frequency offset and the third fractional frequencyoffset.

For an algorithm for fractional frequency offset estimation, by way ofexample, when a preliminary timing synchronization method ({circlearound (2)}) is used,

$R_{{dc},m} = {\sum\limits_{i = 0}^{N - 2}\; {RM}_{i,m}}$i = 0, …  N − 1,

the maximum value thereof is taken, and a corresponding phase ise^(j2πKΔf); Δf can be calculated and converted to the first fractionalfrequency offset value.

When the transmitted preamble symbol contains features required inimplementing the preliminary timing synchronization method ({circlearound (1)}) and the preliminary timing synchronization method ({circlearound (2)}), a fractional frequency offset estimation value is obtainedusing any one or a combination of any two of the first, the second andthe third fractional frequency offset value.

If it is known that the preamble symbol of a transmitting end containstime-domain symbols with two three-segment structures, i.e. C−A−B andB−C−A, at least one time-domain symbol is assembled according to someassembling mode to obtain the preamble symbol; and when judging whetherthe baseband signal contains a united symbol desired to be received, thepreliminary timing synchronization method ({circle around (1)})comprises the following steps:

step S2-1A: according to the predefined acquisition rule and/orpredefined processing rule between segment C, segment A and segment B inthe C−A−B structure and B−C−A structure in the preamble symbol desiredto be received, corresponding inverse processing is performed on thebaseband signal, and delayed moving auto-correlation is performed on thedemodulated signal, so as to obtain basic delayed accumulationcorrelation values (such as U_(1,ca)′(n), U_(1,cb)′(n), U_(1,ab)′(n),U_(2,ca)′(n), U_(2,cb)′(n), and U_(2,ab)′(n) in a C−A−B−B−C−Astructure). The six values can be obtained actually by 3 delayed movingauto-correlators with different delay length, whereU_(1,ca)′(n)=U_(2,ca)′(n)=U_(A, raw)(n);U_(1,cb)′(n)=U_(2,ab)′(n)=U_(A+B, raw)(n); andU_(1,ab)′(n)=U_(2,cb)′(n)=U_(B, raw)(n); therefore, the six values canalso be considered as three values actually, and are defined as 6 valuesfor the convenience of description.

Step S2-1B: basic delayed accumulation correlation values in step S2-1Aare grouped (into three group) according to different delay lengths ofthe delayed moving auto-correlation in the previous step; delayrelationship match and/or phase adjustment are performed on each groupaccording to an specific assembling relationship between two time-domainsymbols, and then mathematical calculation is performed, to obtain afinal accumulation correlation value corresponding to some delay lengthin the previous step; and three final accumulation correlation valueswith different delay lengths are obtained in all.

Step S2-1C: delay match and mathematical calculation are performed onone, two or three of the three final accumulation correlation values, toobtain a correlation value to be detected, i.e. a correlation value forinitial timing synchronization.

Taking an assembling method of C−A−B−B−C−A as an example in particular,assuming that the assembling method of C−A−B−B−C−A is used in thepreamble symbol transmitted by the transmission end, then afterobtaining U_(1,ca)′(n), U_(1,cb)′(n), U_(1,ab)′(n), U_(2,ca)′(n),U_(2,cb)′(n) and U_(2,ab)′(n) in the way mentioned above,U_(1,ca)′(n−(N_(A)+2Len_(B)+Len_(C))) and U_(2,ca)′(n) are added; sincethey are both obtained via the moving auto-correlator with a delaylength of N_(A), a final accumulation correlation value U_(A)(n) with adelay length of N_(A) is obtained.

U_(1,cb)′(n−(N_(A)+2Len_(B))) is added to U_(2,ab)′(n), since they areboth obtained via the moving auto-correlator with a delay length ofN_(A)+Len_(B), a final accumulation correlation value U_(A+B)(n) with adelay length of N_(A)+Len_(B) is obtained.

U_(1,ab)′(n−(2Len_(B))) is added to U_(2,cb)′(n), since they are bothobtained through the moving auto-correlator with a delay length ofLen_(B), a final accumulation correlation value U_(B)(n) with a delaylength of Len_(B) is obtained.

Finally, the correlation result to be detected, i.e. the correlationvalue for initial timing synchronization, is obtained according to thecalculation abs(U_(B)(n))+abs(U_(A+B)(n))+abs(U_(A)(n−Len_(C))).

A block diagram for logical calculations for the result of preliminarytiming synchronization to be detected acquired under the assemblingmethod of C−A−B−B−C−A in this embodiment is provided in FIG. 16, where Ais N_(A), B is Len_(B), and C is Len_(C). In the same way, a blockdiagram for logical calculations for the result of preliminary timingsynchronization to be detected acquired under the assembling method ofB−C−A−C−A−B in this embodiment is provided in FIG. 17, where A is N_(A),B is Len_(B), and C is Len_(C). After the correlation value for initialtiming synchronization is obtained, step S12-2 and step S12-3 above areperformed.

Additionally, in step S2-1A, when FC sequences of 2 time-domain symbolsof the united preamble symbol are the same, a delayed accumulationcorrelation value can be obtained for a combined and assembled part forsegment C+A of two symbols, i.e. the former one and the later one; itcan also be used for calculating the correlation result to be detectedin step S2-1C, to further improve detection performance.

Further, if a transmitting end identifies emergency broadcast byutilizing different assembling mode about the first three-segmentstructure and the second three-segment structure, the initial timingsynchronization method ({circle around (1)}) comprises the followingsteps:

In step S2-1B, the delayed accumulation correlation values of step S2-1A(actually there should be outputs of three delayed movingauto-correlators, but for representation, six delayed movingauto-correlators are defined) are defined as U_(A+B) ¹(n), U_(A) ¹(n)and U_(B) ¹(n), and U_(A+B) ²(n), U_(A) ²(n) and U_(B) ²(n) (a firsttime-domain symbol and a second time-domain symbol respectively), andthe delays are respectively N_(A)+Len_(B), N_(A), and Len_(B). Delayrelationship match is performed on these accumulation correlation valueswith the same delay and/or phase adjustment is performed according to aspecific, splicing relationship and then these accumulation correlationvalues are added and averaged to obtain the final accumulationcorrelation value; since two different splicing modes may exist, delayrelationship match between two different symbols are listed hereinrespectively. Specifically, U_(A+B) ¹(n), U_(A) ¹(n) and U_(B) ¹(n), andU_(A+B) ²(n), U_(A) ²(n) and U_(B) ²(n).

Assuming an assembling method of C−A−B−B−C−A for example,

U_(A) ¹(n−(N_(A)+Len_(C))) is added to U_(A) ²(n), since they are bothobtained through the moving auto-correlator with a delay length ofN^(A), a final accumulation correlation value U_(A)(n) with a delaylength of NA is obtained.

U_(A+B) ¹(n−(N_(A)+2Len_(B))) is added to U_(A−B) ²(n), since they areboth obtained through the moving auto-correlator with a delay length ofN_(A)+Len_(B), a final accumulation correlation value U_(A+B)(n) with adelay length of N_(A)+Len_(B) is obtained.

U_(B) ¹(n−(2N_(A)+2Len_(C))) is added to U_(B) ²(n), since they are bothobtained through the moving auto-correlator with a delay length ofLen_(B), a final accumulation correlation value U_(B)(n) with a delaylength of Len_(B) is obtained.

Finally, a correlation result to be detected for the first branch isobtained according to the calculationabs(U_(B)(n−N_(A)))+abs(U_(A+B)(n))+abs(U_(A)(n)).

Assuming an assembling method of B−C−A−C−A−B for example,

U_(A) ¹(n−(N_(A)+2Len_(B)+Len_(C))) is added to U_(A) ²(n), since theyare both obtained through the moving auto-correlator with a delay lengthof N_(A), a final accumulation correlation value U_(A)(n) with a delaylength of NA is obtained.

U_(A+B) ¹(n−(N_(A)+2Len_(C)) is added to U_(A−B) ²(n), since they areboth obtained through the moving auto-correlator with a delay length ofN_(A)+Len_(B), a final accumulation correlation value U_(A+B)(n) with adelay length of N_(A)+Len_(B) is obtained.

U_(B) ¹(n−(2Len_(B))) is added to U_(B) ²(n), since they are bothobtained through the moving auto-correlator with a delay length ofLen_(B), a final accumulation correlation value U_(B)(n) with a delaylength of Len_(B) is obtained.

Finally, a correlation result to be detected for the second branch isobtained according to the calculationabs(U_(B)(n))+abs(U_(A+B)(n))+abs(U_(A)(n−Len_(C))).

Correlation results to be detected of the 2 branches are finallyobtained according to different delay relationships between symbolscorresponding to the two assembling methods (the C−A−B−B−C−A assemblingmethod and the B−C−A−C−A−B assembling method), wherein if a detectionresult for the first branch satisfy a pre-set condition, then it isdetermined that the baseband signal contains a united preamble symbolwith three-segment structures assembled according to the firstassembling method; if a detection result for the second branch satisfy apre-set condition, then it is determined that the baseband signalcontains a united preamble symbol with three-segment structuresassembled according to the second assembling method; and if it is thecase where the two groups both satisfy the condition, another judgementshould be made, for example, judgement can be made according to theobviousness of the peak-to-noise ratio of the two branches.

Additionally, in step S2-1A, when FC sequences of 2 time-domain symbolsof the united preamble symbol are the same, a delayed accumulationcorrelation value can be obtained for a combined and assembled part forsegment C+A of two time-domain symbols, i.e. the former one and thelater one; in the same way, since two different assembling methods mayexist, a delayed accumulation correlation value can also be obtained fora combined and assembled part for segment C+A of two time-domainsymbols, i.e. the former one and the later one, in the 2 branchesrespectively obtained; and In S2-1C, the value for the 2 branches canalso be respectively used for the mathematical calculation for the 2branches, to obtain a correlation result to be detected for the 2branches, so as to further improve detection performance.

Since the assembled united preamble symbol must adopt any onethree-segment structure, the pre-set condition can be satisfied,regardless of whether a receiving machine makes detection in accordanceto a united preamble symbol or in accordance to a single three-segmentstructure. When a detection result of detecting in accordance to aunited preamble symbol is obviously better than a detection result ofdetecting in accordance to some single preamble symbol, it can bedetermined that the received preamble symbols include time-domainsymbols with a three-segment structures.

Further, satisfaction of the pre-set condition here can not only referto determining whether the pre-set condition is satisfied according to acorrelation result to be detected, but also can refer to the fact thatwhen whether the condition is satisfied cannot be determined enoughaccording to the correlation result to be detected itself, whether thecondition is satisfied is determined according to subsequent othersteps, such as an integer frequency offset estimation and/or decodingresult.

Further, after the initial timing synchronization is preliminarilycompleted, initial timing synchronization results from the preliminarytiming synchronization method ({circle around (1)}) and/or thepreliminary timing synchronization method ({circle around (2)}) can beused for fractional frequency offset estimation.

What is different from the above description of the fractional frequencyoffset estimation is that when the preliminary timing synchronizationmethod ({circle around (1)}) is used, a second fractional frequencyoffset value can be calculated by taking the angle of the maximum valuein U_(A)(n); after conducting conjugate multiplication on U_(A+B)(n) andU_(B)(n−N_(A)) (corresponding to a C−A−B−B−C−A assembling mode) orconducting conjugate multiplication on U_(A+B)(n) and U_(B)(n)(corresponding to a B−C−A−C−A−B assembling mode), a third fractionalfrequency offset value can be calculated by taking the phasecorresponding to the maximum angle. As shown in the schematic portion ofblock diagrams FIG. 16 and FIG. 17 of logical calculations above, anangle is used for obtaining the fractional frequency offset, andfractional frequency offset estimation can be conducted using any one ortwo of the second fractional frequency offset and the third fractionalfrequency offset.

The rest of the description is the same as the description of fractionalfrequency offset estimation above.

With regard to the preliminary timing synchronization method ({circlearound (1)}), taking a preferred united symbol with 4 time-domainsymbols with a three-segment structure as an example, when thearrangement is C−A−B, B−C−A, C−A−B, B−C−A, U_(ca) ¹(n), U_(ab) ¹(n),U_(ab) ¹(n), U_(ca) ²(n), U_(cb) ²(n), U_(ab) ²(n), U_(ca) ³(n), U_(cb)³(n), U_(ab) ³(n), U_(ca) ⁴(n), U_(cb) ⁴(n), and U_(ab) ⁴(n) areobtained. In fact, the 12 values are outputs of 3 delayed movingauto-correlators, and can also be considered as 3 values, and is definedas 12 values for the convenience of expression, where U_(ca) ¹(n)=U_(ca)²(n)=U_(ca) ³(n)=U_(ca) ⁴(n)=U_(A,raw)(n).

U _(cb) ¹(n)=U _(ab) ²(n)=U _(cb) ³(n)=U _(ab) ⁴(n)=U _(A+B,raw)(n).

U _(ab) ¹(n)=U _(cb) ²(n)=U _(ab) ³(n)=U _(cb) ⁴(n)=U _(B,raw)(n).

Delay relationship match and/or phase adjustment between symbols can beperformed on one or more of U_(ca) ¹(n), U_(ca) ²(n), U_(ca) ³(n), andU_(ca) ⁴(n), then addition or average is conducted on same, to obtainthe final U_(A)(n). This is because they have the same phase value. Anexample of delay match is as follows:

U_(ca) ¹(n−2(N_(A)+Len_(B)+Len_(C))−(N_(A)+2Len_(B)+Len_(C))),

U_(ca) ²(n−2(N_(A)+Len_(B)+Len_(C))),

U_(ca) ³(n−(N_(A)+2Len_(B)+Len_(C))), and

U_(ca) ⁴(n)

Delay relationship match and/or phase adjustment between symbols can beperformed on one or more of U_(cb) ¹(n), U_(ab) ²(n), U_(cb) ³(n), andU_(ab) ⁴(n), and then addition or average is conducted on same, toobtain the final U_(A+B)(n). This is because they have the same phasevalue. An example of delay match is as follows:

U_(cb) ¹(n−2(N_(A)+Len_(B)+Len_(C))−(N_(A)+2Len_(B))),

U_(ab) ²(n−2(N_(A)+Len_(B)+Len_(C))),

U_(cb) ³(n−(N_(A)+2Len_(B))), and

U_(ab) ⁴(n).

Delay relationship match and/or phase adjustment between symbols can beperformed on one or more of U_(ab) ¹(n), U_(cb) ²(n), U_(ab) ³(n), andU_(cb) ⁴(n), and then addition or average is conducted on same, toobtain the final U_(B)(n). An example of delay match is as follows:U_(ab) ¹(n−2(N_(A)+Len_(B)+Len_(C))−(2Len_(B)))

U_(cb) ²(n−2(N_(A)+Len_(B)+Len_(C))),

U_(ab) ³(n−(2Len_(B))), and

U_(cb) ⁴(n)

Finally, delay match and a specific calculation are performed againbased on one or more of U_(A)(n) and U_(A+B)(n) and U_(B)(n), and anexample of delay match herein is as follows:

U_(A)(n), U_(A+B)(n), and U_(B)(n−N_(A))

initial timing synchronization is accomplished by utilizing ancalculation result, and the specific calculation may be absolute valueaddition. For example, the initial timing synchronization isaccomplished by taking the position of the maximum value.

It should be noted that, considering the influence of sampling offset insystem, in the above-mentioned embodiment, a delay number that thereshould be can be adjusted in a certain range, for example, incrementingor decrementing the delay number in some delayed correlator by one, toobtain three delay numbers, i.e. the delay number per se, the delaynumber incremented by one, and the delay number decremented by one; thena plurality of delayed moving auto-correlation are then performedaccording to the obtained adjusted delay numbers and the delay numberthat there should be, for example, implementing delayed movingauto-correlation according to the three delay numbers, then selectingthe one with the most obvious correlation result; at the same time, atiming offset can be estimated using the correlation result.

FIG. 18 provides a block diagram of logical calculation for realizingpreliminary timing synchronization using 4 sets of accumulationcorrelation values of 4 time-domain symbols in this embodiment; and FIG.19 provides a block diagram of logical calculation for realizingpreliminary timing synchronization using 2 sets of accumulationcorrelation values of 2 time-domain symbols in this embodiment.

Without loss of generality, if the preamble symbol contains othertime-domain properties besides having a C−A−B or B−C−A structure,besides using the timing synchronization method with the above-mentionedC−A−B or B−C−A structural feature, using other timing synchronizationmethods implemented directed at other time domain structural featuresdoes not depart from the scope of the present invention.

Additionally, the principle of the method for fractional frequencyoffset estimation of a plurality of time-domain symbols with athree-segment structure is the same as that mentioned above, which willnot be described here anymore.

Continuously, description is made with respect to the preliminary timingsynchronization method ({circle around (1)}) for K time-domain symbolswith a three-segment structure, wherein a first time-domain symbol has aCAB structure, and the follow-ups are BCA structures connectedsuccessively.

There are two different three-segment structures, i.e. a CAB structureand a BCA structure; then in the CAB structure, when truncating A togenerate a postfix or hyper prefix (part B), the position on thetime-domain main body signal A corresponding to the start point oftruncation is called a first sampling point serial number N1_1, and inthe BCA structure, when truncating A to generate a postfix or hyperprefix (part B), the position on the time-domain main body signal Acorresponding to the start point of truncation is called a secondsampling point serial number N1_2, where N1_1 and N1_2 satisfy apredefined restriction relationship formulaN1_1+N1_2=2N_(A)−(Len_(B)+Len_(c)), and N1_1+Len_(B)=N_(A).

Specifically, as an example, assuming that N_(A) is 2048, Len_(C) is520, Len_(B)=504, N1_1=1544, and N1_2=1528, f_(SH)=1/(2048T).

By way of example, the formula of acquiring an accumulation correlationvalue through delayed moving auto-correlation:

$\begin{matrix}{{{U_{ca}(n)} = {r\; (n)\; {r^{*}\left( {n - N_{A}} \right)}}}{{U_{ca}^{\prime}(n)} = {\frac{1}{{Len}_{\; C}}{\sum\limits_{k = 0}^{{Len}_{\; C} - 1}\; {U_{ca}\left( {n - k} \right)}}}}} & \left( {{Formula}\mspace{14mu} 53\text{-}1\text{;}\mspace{14mu} 53\text{-}2} \right)\end{matrix}$

U_(1s)′(n) can be obtained by conducting energy normalization on U₁′(n).

That is,

$\begin{matrix}{{U_{ca}^{\prime}(n)} = \frac{U_{ca}^{\prime}(n)}{0.5\frac{1}{{Len}_{\; C}}{\sum\limits_{k = 0}^{{Len}_{\; C} - 1}\; \left( {{{r\left( {n - k} \right)}}^{2} + {{r\left( {n - k - N_{A}} \right)}}^{2}} \right)}}} & \left( {{Formula}\mspace{14mu} 54} \right)\end{matrix}$

Energy normalization can also be conducted in another way; and theconjugate operation * in U₁(n) can also be realized by performingconjugate operation * on r(n), and no conjugate operation is performedon r(n−N_(A)).

In each C−A−B or B−C−A structure, three accumulation correlation valuesof CA, AB and BC based on the same content can be respectively acquired.

Delayed moving correlation is conducted using the same part in segment Cand segment A; note that the above-mentioned step of energynormalization can be added, which will not be described any more. Threecorrelation values can be obtained from each C−A−B or B−C−A structure:U_(ca)′(n), U_(cb)′(n), and U_(cb)′(n)

$\begin{matrix}{{{U_{1}(n)} = {r\; (n)\; {r^{*}\left( {n - N_{A}} \right)}}}{{U_{ca}^{\prime}(n)} = {\frac{1}{{Len}_{\; C}}{\sum\limits_{k = 0}^{N_{CP} - 1}\; {U_{1}\left( {n - k} \right)}}}}} & \left( {{Formula}\mspace{14mu} 55\text{-}1\text{;}\mspace{14mu} 55\text{-}2} \right)\end{matrix}$

Delayed moving correlation is conducted using a corresponding part insegment B and segment C:

When the C−A−B structure is adopted,

$\begin{matrix}{{{U_{2}(n)} = {{r\; (n)\; {r^{*}\left( {n - N_{A} - N_{A} + {{N1\_}1}} \right)}e^{{- j}\; n\; f_{SH}T}} = {r\; (n){r^{*}\left( {n - N_{A} - {Len}_{B}} \right)}e^{{- {jnf}_{SH}}T}}}}\mspace{79mu} {{U_{cb}^{\prime}(n)} = {\frac{1}{corr\_ len}{\sum\limits_{k = 0}^{N_{CP} - 1}\; {U_{2}\left( {n - k} \right)}}}}} & \left( {{Formula}\mspace{14mu} 56\text{-}1\text{;}\mspace{14mu} 56\text{-}2} \right)\end{matrix}$

When the C−B−A structure is adopted,

$\begin{matrix}{{{U_{2}(n)} = {{r\; (n)\; {r^{*}\left( {n - \left( {{{N1\_}2} - N_{A} + {Len}_{c} + {Len}_{B}} \right)} \right)}e^{{- j}\; n\; f_{SH}T}} = {r\; (n){r^{*}\left( {n - \left( {Len}_{B} \right)} \right)}e^{{- {jnf}_{SH}}T}}}}\mspace{79mu} {{U_{cb}^{\prime}(n)} = {\frac{1}{corr\_ len}{\sum\limits_{k = 0}^{N_{CP} - 1}\; {U_{2}\left( {n - k} \right)}}}}} & \left( {{Formula}\mspace{14mu} 57\text{-}1\text{;}\mspace{14mu} 57\text{-}2} \right)\end{matrix}$

Delayed moving correlation is conducted using a corresponding part insegment B and segment A:

in the case of the C−A−B structure,

$\begin{matrix}{{{U_{3}(n)} = {{r\; (n)\; {r^{*}\left( {n - N_{A} + {{N1\_}1}} \right)}e^{{- j}\; n\; f_{SH}T}} = {r\; (n){r^{*}\left( {n - {Len}_{B}} \right)}e^{{- {jnf}_{SH}}T}}}}\mspace{79mu} {{U_{ab}^{\prime}(n)} = {\frac{1}{corr\_ len}{\sum\limits_{k = 0}^{N_{CP} - 1}\; {U_{3}\left( {n - k} \right)}}}}} & \left( {{Formula}\mspace{14mu} 58\text{-}1\text{;}\mspace{14mu} 58\text{-}2} \right)\end{matrix}$

in the case of the C−B−A structure,

$\begin{matrix}{{{U_{3}(n)} = {{r\; (n)\; {r^{*}\left( {n - {{N1\_}2} - {Len}_{B} - {Len}_{C}} \right)}e^{{- j}\; n\; f_{SH}T}} = {r\; (n){r^{*}\left( {n - N_{A} - {Len}_{B}} \right)}e^{{- {jnf}_{SH}}T}}}}\mspace{79mu} {{U_{ab}^{\prime}(n)} = {\frac{1}{corr\_ len}{\sum\limits_{k = 0}^{N_{CP} - 1}\; {U_{3}\left( {n - k} \right)}}}}} & \left( {{Formula}\mspace{14mu} 59\text{-}1\text{;}\mspace{14mu} 59\text{-}2} \right)\end{matrix}$

where corr_len can be valued 1/f_(SH)T to avoid continuous waveinterference, or can be valued Len_(B) to enable a peak to be sharp.

When the preamble symbol contains a plurality of time-domain symbols,and the time-domain symbols adopt a three-segment structure, threeaccumulation correlation values of CA, AB and CB can be obtained, i.e.U_(ca)′(n), U_(cb)′(n), and U_(ab)′(n); an accumulation correlationvalue is obtained by any one or at least any two of U_(ca)′(n),U_(cb)′(n), and U_(ab)′(n); delay relationship match and/or mathematicalcalculation between one or more symbols based on the accumulationcorrelation value, to obtain a final calculation value; and the finalcalculation value is used for initial synchronization.

For example, with respect to K time-domain symbols with a three-segmentstructure, when the arrangement is C−A−B, B−C−A, B−C−A, B−C−A, . . . ,B−C−A, i.e. the first symbol is of the C−A−B structure, and thefollowing K−1 symbols are all of the B−C−A structure, U_(ca) ¹(n),U_(cb) ¹(n), U_(ab) ¹(n), U_(ca) ²(n), U_(cb) ²(n), U_(ab) ²(n), U_(ca)³(n), U_(cb) ³(n), U_(ab) ³(n), U_(ca) ⁴(n), U_(cb) ⁴(n), U_(ab) ⁴(n), .. . U_(ca) ^(K)(n), U_(cb) ^(K)(n), and U_(ab) ^(K)(n) are obtained. Infact, the above-mentioned correlation values are outputs of threedelayed moving auto-correlators,

where U _(ca) ¹(n)=U _(ca) ²(n)= . . . =U _(ca) ^(K)(n);

U _(cb) ¹(n)=U _(ab) ²(n)= . . . U _(ab) ^(K)(n); and

U _(ab) ¹(n)=U _(cb) ²(n)= . . . U _(cb) ^(K)(n);

then, delay relationship match and/or phase adjustment between symbolscan be performed on one or more of, U_(ca) ¹(n), U_(ca) ²(n), U_(ca)³(n), U_(ca) ⁴(n), . . . U_(ca) ^(K)(n) according to the relationshipbetween one and more symbols, and then addition or average is conductedon same, to obtain the final U_(A)(n).

This is because they have the same phase value. When only one symbol isadopted, the delay relationship match and/or phase adjustment areactually equivalent to performing no operation.

The delay match and/or phase adjustment contain all or some of thefollowing, with an example provided below:

U_(ca) ¹(n−(K−2)·(N_(A)+Len_(B)+Len_(C))−(N_(A)+2Len_(B)+Len_(C))),

U_(ca) ²(n−(K−2)·(N_(A)+Len_(B)+Len_(C))), . . . U_(ca)^(j)(n−(K−j)·(N_(A)+Len_(B)+Len_(C))),

U_(ca) ^(K−1)(n−(N_(A)+Len_(B)+Len_(C))), and

U_(ca) ^(K)(n)

where considering that in the embodiment f_(SH)=1/(2048T), N^(A) is2048, Len_(C) is 520, and Len_(B)=504, i.e.(N_(A)+Len_(B)+Len_(C))=3072, phase adjustment should be performed onU_(ca) ³(n−(N_(A)+Len_(B)+Len_(C))) by multiplying e^(jπ).

Delay relationship match and/or phase adjustment can be performed on oneor more of U_(cb) ¹(n), U_(ab) ²(n), U_(ab) ³(n), U_(ab) ⁴(n), . . .U_(ab) ^(K)(n) according to the relationship between one and moresymbols. Since they have the same phase value, they can then be added oraveraged, to obtain a final U_(A+B)(n). When only one correlation valueis adopted, the delay relationship match and/or phase adjustment areactually equivalent to performing no operation. This is because theyhave the same phase value. The delay match result contains all or someof the following, with an example provided below:

U_(cb) ¹(n−(K−2)·(N_(A)+Len_(B)+Len_(C))−(N_(A)+2Len_(B))),

U_(ab) ²(n−(K−2)·(N_(A)+Len_(B)+Len_(C))), . . . U_(ab)^(j)(n−(K−j)·(N_(A)+Len_(B)+Len_(C)))

U_(ab) ^(K−1)(n−(N−_(A)+Len_(B)+Len_(C))), and

U_(ab) ^(K)(n).

where considering that in the embodiment f_(SH)=1/(2048T), N_(A) is2048, Len_(C) is 520, and Len_(B)=504, i.e.(N_(A)+Len_(B)+Len_(C))=3072, phase adjustment should be performed onU_(ab) ³(n−(N_(A)+Len_(B)+Len_(C))) by multiplying e^(jπ).

Delay relationship match and/or phase adjustment between symbols can beperformed on one or more of U_(ab) ¹(n), U_(cb) ²(n), U_(cb) ³(n),U_(cb) ⁴(n), . . . U_(cb) ^(K)(n) according to the correspondingrelationship between one and more symbols, and then addition or averageis conducted on same, to obtain the final U_(B)(n). When only onecorrelation value is adopted, the delay relationship match and/or phaseadjustment are actually equivalent to no operation. The delay matchresult contains all or some of the following, with an example providedbelow:

U_(ab) ¹(n−(K−2)·(N_(A)+Len_(B)+Len_(C))−(2Len_(B))),

U_(cb) ²(n−(K−2)·(N_(A)+Len_(B)+Len_(C))), . . . U_(cb)^(j)(n−(K−j)·(N_(A)+Len_(B)+Len_(C)))

U_(cb) ^(K−1)(n−(N_(A)+Len_(B)+Len_(C))), and

U_(cb) ^(K)(n).

where considering that in the embodiment f_(SH)=1/(2048T), N_(A) is2048, Len_(C) is 520, and Len_(B)=504, i.e.(N_(A)+Len_(B)+Len_(C))=3072, U_(cb) ³(n−(N_(A)+Len_(B)+Len_(C))) needsto be multiplied by e^(jπ).

Finally, delay match and a specific calculation are performed againbased on one or more of U_(A)(n) and U_(A+B)(n), and U_(B)(n), and thedelay match result herein contains all or some of the following, with anexample provided below:

U_(A)(n), U_(A+B)(n), and U_(B)(n−N_(A))

initial timing synchronization is accomplished by utilizing ancalculation result, and the specific calculation may be absolute valueaddition. For example, the initial timing synchronization isaccomplished by taking the position of the maximum value.

Step S12-2 contains the initial timing synchronization method forpreliminarily determining the position of the preamble symbol in aphysical frame. Further, after initial synchronization, the integerfrequency offset estimation can further be conducted based on a resultobtained from the initial timing synchronization method.

Further, when the time-domain main body signal A correspond to theabove-mentioned frequency-domain structure I, the receiving end can alsoperform an integer frequency offset estimation using a fixed sequence,that is, the preamble symbol of the present invention can also be usedfor the integer frequency offset estimation in the following steps:

1) truncating a signal containing the fixed subcarrier, according to thedetermined position of the preamble symbol in the physical frame;

2) performing calculation on the received signal containing a fixedsubcarrier, with a frequency-domain fixed subcarrier sequence or atime-domain signal corresponding to the frequency-domain fixedsubcarrier sequence, so as to realize an integer frequency offsetestimation.

Explanation below is provided for the integer frequency offsetestimation method based on the result of the initial timingsynchronization, and the steps of the integer frequency offsetestimation include any one or a combination of any two of the particularmethods below:

a first integer frequency offset estimation method contains: accordingto a result of the initial timing synchronization, truncating to get asection of time-domain signal containing the entirety or a portion ofthe time-domain main body signal, modulating the truncated section oftime-domain signal with different frequency offsets in a frequencysweeping manner, to obtain N frequency sweeping time-domain signalscorresponding to the offset values on a one-to-one basis, and afterperforming moving correlation between a known time-domain signalobtained by performing inverse transform on a known frequency-domainsequence and each frequency sweeping time-domain signal, comparing themaximum correlation peaks of N correlation results, regarding afrequency offset value by which a frequency sweeping time-domain signalcorresponding to the maximum correlation result is modulated as theinteger frequency offset estimation value; and/or a second integerfrequency offset estimation method contains:

performing Fourier transform on the time-domain signal which istruncated to the length of the time-domain main body signal according tothe result of the initial timing synchronization, conducting cyclicshift on the obtained frequency-domain subcarriers using different shiftvalues within a frequency sweeping range, truncating a received sequencecorresponding to a valid subcarrier, performing predefined calculationand then inverse transform on the received sequence and the knownfrequency-domain sequence, performing selection from several groups ofinverse transform results corresponding to the shift values on aone-to-one basis to obtain a an optimum shift value, and obtaining theinteger frequency offset estimation value according to a correspondingrelationship between the shift value and the integer frequency offsetestimation value.

The integralfrequency offset estimation method is described inparticular by way of example. For example, the time-domain main bodysignal A correspondingly has the above-mentioned frequency-domainstructure I, that is, a frequency-domain OFDM symbol comprises threeparts respectively, i.e. virtual subcarriers, signalling sequence(referred to as SC) subcarriers and fixed sequence (referred to as FC)subcarriers, then a known frequency-domain sequence recited below is afixed subcarrier; for another example, the time-domain main body signalcorrespondingly has the above-mentioned frequency-domain structure II,that is, the first time-domain symbol of the preamble symbol is knowninformation, then a known frequency-domain sequence recited belowcorresponds to the first time-domain symbol.

The first integer frequency offset estimation method contains: accordingto a result of the initial timing synchronization, truncating to get asection of time-domain waveform containing the entirety or a portion ofthe time-domain main body signal, modulating the section of time-domainwaveform with different frequency offsets in a frequency sweeping mode,i.e. in a fixed frequency changing step, such as corresponding to aninteger subcarrier spacing, to obtain several time-domain signals,

A1_(y)(nT)=r(nT)·e ^(j2πynTf) ^(s) ^(/N) ^(A)   (Formula 60)

where T is the sampling period, and f_(s) is the sampling frequency. Thetime-domain signal obtained by filling with known frequency-domainsequence in a predefined subcarrier filling mode and performing inverseFourier transform on same is A2; and moving correlation is performed onA2, which is taken as a known signal, and each A1_(y), so as to selectthe A1_(y) which corresponds to the maximum correlation peak, then thecorresponding modulation frequency offset value y is the integralmultiple of frequency offset estimation value.

The frequency sweeping range corresponds to a frequency offset rangerequirement that the system needs to meet, for example, the system needsto cope with a frequency offset of 500 k, and a sampling rate of thesystem is 9.14M, and the main body of the preamble symbol has a lengthof 2 k, then the frequency sweeping range is

${\pm \left\lceil \frac{500\mspace{11mu} K \times 2048}{9.14\mspace{11mu} M} \right\rceil},$

i.e. [−114, 114].

The second integer frequency offset estimation method contains:according to the position where the preamble symbol appears detected bythe initial timing synchronization, truncating to get the time-domainmain body signal A, and performing FFT on same; performing cyclic shiftwith different shift values on the frequency-domain subcarrier after FFTin a frequency-sweeping range; after that, truncating to get a receivedsequence corresponding to a valid subcarrier; performing somecalculation (generally, conjugate multiplication, or division) on thereceived sequence and the known frequency-domain sequence; performingIFFT on a result of the calculation; and performing specific calculationon a result of the IFFT, such as taking the path with the largestenergy, or taking the accumulation of several paths with large energies.With the several shift values, after several times of IFFT, severalcalculation results will be obtained. Which shift value corresponds tothe integer frequency offset estimation is judged based on the severaloperation results, thus obtaining an integer frequency offset estimationvalue.

A typical judgement method is based on several results, and a shiftvalue corresponding to the result with the maximum energy is selected asthe integer frequency offset estimation value.

When the time-domain main body signal A corresponds to theabove-mentioned frequency-domain structure I, the following integralfrequency offset estimation method can also be adopted.

The integer frequency offset estimation method comprises: truncatingsome symbols in a preamble symbol to get a time-domain main body signalA and performing Fourier transform on same to obtain a frequency-domainOFDM symbol, performing cyclic shift in the frequency sweeping range onthe frequency-domain OFDM symbol obtained by transform, conductinginterlaced differential multiplication according to the position of theFC on the subcarrier and an interval between two fixed sequencesubcarriers, i.e. the former one and the later one, and performingcorrelation calculation on interlaced differential multiplication valueof the known fixed sequence subcarriers to obtain a series ofcorrelation values, and selecting the cyclic shift corresponding to themaximum correlation value, thus being able to accordingly obtain theintegral frequency offset estimation value.

Further, when it is determined that the baseband signal contains apreamble symbol containing a C−A−B and B−C−A cascaded three-segmentstructure desired to be received, if the positions of thefrequency-domain valid subcarriers of the 2 time-domain symbols, i.e.the former one and the later one, differ from each other by an evennumber of cyclic shift values, Fourier transform can be performed on thetime-domain main body signals A of the 2 time-domain symbols to obtain 2frequency-domain OFDM symbol; then the same cyclic shift is performed onthe 2 frequency-domain OFDM symbols, which are obtained through thetransform, in the above-mentioned frequency sweeping range at the sametime; conjugate multiplication is performed on a received value of eachshifted symbol and the known fixed sequence subcarrier value of thesymbol; and after conjugate multiplication is again performed onmultiplication values on the same subcarrier position of the 2frequency-domain OFDM symbols, the conjugate multiplication values ofall the valid FC subcarriers at common positions of the 2frequency-domain OFDM symbols,

That is,

$\begin{matrix}{{{corr}_{j} = {{Re}\left( {\sum\limits_{i = 0}^{M - 1}\; {R_{i,1,j}{{FC}_{i,1}^{*}\left( {R_{i,2,j}{FC}_{i,2}^{*}} \right)}^{*}}} \right)}}\; {j \in \mspace{11mu} {{frequency}\mspace{14mu} {sweeping}\mspace{14mu} {range}}}} & \left( {{Formula}\mspace{14mu} 61} \right)\end{matrix}$

R_(i,1,j) is a received value of the first frequency-domain symbolcorresponding to the FC position after a shift of j, R_(i,2,j) is areceived value of the second frequency-domain symbol corresponding tothe FC position after a shift of j, FC*_(i,1) and FC*_(i,2) arerespectively a known FC value on some subcarrier of the first symbol andthe second symbol, and M is the number of the known FCs. In this way, aseries of accumulation values corresponding to various cyclic shiftvalues are obtained, and an integer frequency offset estimation valuecan be accordingly obtained using a cyclic shift corresponding to themaximum accumulation value.

There are many particular algorithms for integer frequency offsetestimation, which will not be described here anymore.

Further, after the integer frequency offset estimation, the frequencyoffset is compensated, and thus the transmitted signalling is parsed.

Further optionally, after the integral frequency-offset estimation isaccomplished, precise timing synchronization is performed using theknown information in the preamble symbol.

For example, when the frequency-domain structure I is adopted, finetiming synchronization is conducted using a fixed subcarrier sequence(FC) contained by one or more time-domain symbols; and

for another example, when the frequency-domain structure II is adopted,if the first time-domain main body signal in at least one time-domainmain body signal is a known signal, a fine timing synchronization methodis conducted using the known signal.

In the case where the above-mentioned judgement result in step S12-3 isyes, the step of determining the position of the preamble symbol in thephysical frame and resolving signalling information carried by thepreamble symbol will be described in detail below, and the stepcontains:

determining the position of the preamble symbol, comprising: based on adetection result satisfying a pre-set condition, determining theposition of the preamble symbol in the physical frame; and

if a preamble symbol desired to be received exists, determining theposition where the preamble symbol appears according to a greatcorrelation value to be detected or the greatest correlation value to bedetected.

The step of parsing transmitted signalling further contains a channelestimation method.

For example, in the case of having the frequency-domain structure I,channel estimation is accomplished using a received signal containingthe fixed sequence subcarrier and a known frequency-domain fixedsubsequence subcarrier and/or a time-domain signal obtained byperforming inverse Fourier transform thereon, and this can also chosento be carried out in the time domain and/or in the frequency domain,which will not be described here anymore.

The channel estimation method comprises: when the decoding of theprevious time-domain main body signal is achieved, using decodedinformation obtained as sending information, to perform channelestimation again in the time domain/frequency domain, and performingsome specific calculation on it with a previous channel estimationresult to obtain a new channel estimation result, for use in parsingsignalling of the next time-domain main body signal.

Further, when a frame format parameter and/or an emergency broadcastcontent in the preamble symbols is resolved, the position of asubsequent signalling symbol and the position of a data symbol can beobtained according to the content of the parameter and the determinedposition of the preamble symbol, and is used to parse subsequentsignalling symbol or data symbol.

The step of resolving signalling information carried by the preamblesymbol in step S12-3 is explained continuously. The step of parsing asignalling signal comprises: resolving signalling information carried bythe preamble symbol by utilizing the entirety or a portion of atime-domain waveform of the preamble symbol and/or a frequency-domainsignal obtained from the entirety or a portion of the time-domainwaveform of the preamble symbol through Fourier transform.

The signalling parsing process is explained with respect to thefrequency-domain structure I below.

The signalling information carried by signalling sequence subcarriers inthe preamble symbol is resolved by performing calculation using thereceived signal and a set of known signalling sequence subcarrierscontaining the signalling sequence subcarriers, or a time-domain signalcorresponding to the set of signalling sequence subcarriers. The set ofsignalling sequence subcarriers is produced based on a set of knownsignalling sequences.

The signal containing the signalling sequence subcarriers comprises: theentire or a partial of a time-domain waveform of the received preamblesymbol, and one or more frequency-domain OFDM symbols obtained byperforming Fourier transform on one or more time-domain OFDM symbolstruncated from the preamble symbol. The set of signalling sequencesubcarriers is a set formed by filling the valid subcarriers withvarious signalling sequences in the set of signalling sequences.

Specifically, one or more frequency-domain OFDM symbols are obtained byperforming Fourier transform on one or more truncated time-domain symbolcorresponding to the length N_(A) of the OFDM symbol; then zerosubcarriers are removed, and one or more received frequency-domainsignalling subcarriers are taken out according to the positions of thesignalling subcarriers. A specific mathematical calculation is conductedon the one or more received frequency-domain signalling subcarriers withthe above-mentioned channel estimation value and the known set ofsignalling sequence subcarriers, to complete a frequency-domain decodingfunction.

For example, let i=0:M−1, M be the number signalling subcarriers, andj=0:2^(P)−1, P denotes the number of bits of signalling transmitted inthe frequency domain, that is, the corresponding set of signallingsubcarriers has 2^(P) elements in total, and each element corresponds toa sequence with a length of M; H_(i) be a channel estimation valuecorresponding to each signalling subcarrier, SC_rec_(i) be a receivedfrequency-domain signalling subcarrier value, and SC_(i) ^(j) be the ithvalue of the ^(j)th element in the set of signalling sequencesubcarriers. Then

${{corr}_{j} = {{Re}\left( {\sum\limits_{i = 0}^{M - 1}\; {{SC\_ rec}_{i}H_{i}^{*}{SC}_{i}^{*j}}} \right)}}\;$j = 0:2^(P) − 1,

information about the signalling transmitted in the frequency domain canbe obtained by taking j corresponding to max(corr_(j)).

In other embodiments, the previous process can also be carried out inthe time domain; and the information about the signalling transmitted inthe frequency domain can also be resolved by filling with zeros atappropriate positions of the known set of signalling sequencesubcarriers to generate a frequency-domain symbol with a correspondinglength, then performing inverse Fourier transform to obtain a set oftime-domain signalling waveforms, directly conducting synchronouscorrelation on the set of waveforms with a received time-domain signalof which the accurate position has been acquired, then taking acorrelation value with the maximum absolute value, which will not bedescribed here anymore.

The signalling parsing process is explained with respect to thefrequency-domain structure II below.

For example, after an FFT calculation with a corresponding length isperformed on a time-domain main body signal with a length N_(FFT)corresponding to the position section A, zero subcarriers are removed;and the received frequency-domain subcarriers are taken out according tothe positions of the valid subcarriers, and are used for parsingsignalling.

If a transmitted sequence has been PN modulated, then the receiving endcan firstly perform a PN demodulation operation on the receivedfrequency-domain subcarrier, and then parse the signalling of a ZCsequence. It is also possible to directly parse the signalling usingfrequency-domain subcarriers without PN modulation. The difference onlylies in that sets of known sequences are different, which will beelaborated below.

Further, in the step of parsing signalling information, the transmittingend parses the signalling using a set of known signalling sequenceproduced by all possible different root values and/or differentfrequency-domain shift values of the transmitted frequency-domain mainbody sequence, and all possible frequency-domain modulation frequencyoffset values. The set of known sequences here contains the followingsignificance:

if PN modulation is performed at the transmitting end on a CAZACsequence produced by all possible root values and/or all possiblefrequency-domain cyclic shifts, then the set of known sequences can notonly refer to a set of PN-modulated sequences, but also can refer to aset of sequences without PN modulation. If the receiving end performs aPN demodulation operation in the frequency domain, then the set of knownsequences adopts the set of sequences without PN modulation; and if thereceiving end does not perform PN demodulation in the frequency domain,then the set of known sequences adopts the set of PN-modulatedsequences. If a time-domain waveform corresponding to the set of knownsequences is to be used, then the set of PN-modulated sequences of theCAZAC sequence must be used.

Further, if the transmitting end also conducts an interleave operationafter generating the CAZAC sequence, then the set of known sequences cannot only refer to the ZACAC sequence and/or the set of PN-modulated andfrequency-domain interleaved sequences, but also can refer to the set ofsequences without frequency-domain interleave. If the receiving endperforms a de-interleave operation in the frequency domain, then the setof known sequences adopts the set of sequence without frequency-domaininterleave; and if the receiving end does not perform de-interleave inthe frequency domain, then the set of known sequences adopts the set offrequency-domain interleaved sequences. If a time-domain waveformcorresponding to the set of known sequences is to be used, then theZACAC sequence and/or the set of PN-modulated and de-interleavedsequences must be used, i.e. a set consisting of various sequencesfinally mapped onto the subcarriers.

The following description is made to the particular process signallingparsing respectively from two transmission situations adopted by thegeneration method of the transmitting end.

<First transmission situation> In a process of generating thefrequency-domain subcarrier, after a sequence is generated usingdifferent sequence generation formulas and/or a sequence is generatedbased on the same sequence generation formula, cyclic shift is furtherperformed on the generated sequence,

a specific mathematical calculation is performed on the frequency-domainsignalling subcarrier and the channel estimation value, and all possiblefrequency-domain main body sequence, so as to realize signallingparsing, wherein the specific mathematical calculation containing anyone of the following:

(1) maximum likelihood correlation operation combined with channelestimation; or

(2) performing channel equalization on the frequency-domain signallingsubcarrier using the channel estimation value, then performingcorrelation calculation on an equalized signal with all of the possiblefrequency-domain main body sequence, and selecting the maximumcorrelation value as a decoding result of signalling parsing.

The process of signalling parsing under the first transmitting situationis described in particular below.

For example, let i=0:M⁻¹, M be the number of signalling subcarriers, andj=0:2^(P)−1, P denotes the number of bits of signalling transmitted inthe frequency domain, that is, the corresponding set of signallingsubcarriers has 2 ^(P) elements in total, and each element correspondsto a sequence with a length of M; H_(i) be a channel estimation valuecorresponding to each signalling subcarrier, SC_rec_(i) be a receivedfrequency-domain signalling subcarrier value, and SC_(i) ^(j) be the ithvalue of the ^(j)th element in the set of signalling subcarriers.

Then

$\begin{matrix}{{{corr}_{j} = {{Re}\left( {\sum\limits_{i = 0}^{M - 1}\; {{SC\_ rec}_{i}H_{i}^{*}{SC}_{i}^{*j}}} \right)}}\; j = {{0\text{:}2^{P}} - 1}} & \left( {{Formula}\mspace{14mu} 62} \right)\end{matrix}$

The signalling transmitted in the frequency domain can be obtained bytaking j corresponding to max(corr_(j)).

If the transmitting end performs PN modulation, and PN demodulation isnot performed on SC_rec_(i), SC_(i) ^(j) then accordingly adopt the setof PN-modulated sequences; and if PN demodulation is performed onSC_rec_(i), then SC_(i) ^(j) accordingly adopt the set of sequenceswithout PN modulation.

With regard to the situation where the transmitting end contains afrequency-domain interleave operation, it can be simply inferred, whichwill not be specially elaborated here anymore.

Optionally, the process of decoding frequency-domain transmissionsignalling can also be carried out in the time domain; and thesignalling transmitted in the frequency domain can also be resolved byperforming IFFT transform on the set of known signalling subcarrier toobtain a corresponding set of time-domain signalling waveforms, directlyconducting synchronous correlation on the obtained set of time-domainsignalling waveforms with a received time-domain signal of which theaccurate position has been acquired, which will not be described hereinanymore.

If the signalling subcarriers of each symbol is obtained by performingPN modulation on more than one ZC sequence before frequency-domaininterleave, then after obtaining the valid frequency-domain subcarriers,the receiving end performs a corresponding frequency-domainde-interleave operation and a PN demodulation operation, and thenparsing the signalling of the ZC sequence. If the PN modulation isbefore the frequency-domain interleave, then frequency-domainde-interleave is performed first, and then PN demodulation is performed.If the PN modulation is after the frequency-domain interleave, then PNdemodulation is performed first, then frequency-domain de-interleave isperformed; or frequency-domain de-interleave is performed first, andthen PN demodulation is performed. However, a PN sequence used fordemodulation at this time is a PN sequence obtained by de-interleavingan original PN.

<Second transmission situation> In the process of generating thefrequency-domain subcarriers, phase modulation is performed on apre-generated subcarrier with the frequency offset value.

In general, the predefined sending rule required to be satisfiedcontains: obtaining pre-generated subcarriers by processing afrequency-domain main body sequence corresponding to a time-domain mainbody signal in each transmitted time-domain signal, and performing phasemodulation with a predefined frequency offset value S on each validsubcarrier or performing cyclic shift with a predefined shift value onthe time-domain signal after inverse Fourier transform. A symbol fortransmitting a basic parameter contained in the preamble symbol isreferred to as a PFC symbol in the following.

Specifically, in the step of resolving signalling information carried bythe preamble symbol using the frequency-domain signal, if thefrequency-domain sequence in the transmitting end is generated byperforming phase modulation on each valid subcarrier according to theabove-mentioned frequency offset value S, then a parsing and receivingalgorithm that can be implemented include the following 3 examples ofsignalling parsing, which are <example I of signalling parsing>,<example II of signalling parsing> and <example III of signallingparsing> respectively.

<Example I of Signalling Parsing>

Description is made directed at example I of signalling parsing:performing an FFT calculation on the time-domain main body signal Acorresponding to each time-domain symbol in the preamble symbolgenerated according to the above-mentioned rule, to obtain afrequency-domain signal; taking out the value of valid subcarriers inthe frequency-domain signal; after performing a predefined mathematicalcalculation on each subcarrier with the subcarrier corresponding to eachknown frequency-domain sequence of the set of known frequency-domainsignalling of the symbol, conducting IFFT calculation, wherein eachknown frequency-domain sequence corresponds one IFFT result, and eachsymbol corresponds to one or more IFFT results; selecting the mostreliable IFFT result of each symbol, and performing predefinedprocessing; then using a processing result between a plurality ofsymbols to further perform some calculation between symbols to resolveinformation about the transmitted signalling (including signallingconveyed using different frequency-domain sequences and/or signallingconveyed transmitted using a frequency-domain modulation frequencyoffset value, i.e. a time-domain cyclic shift value).

The set of frequency-domain known signalling contains all possiblefrequency-domain sequences of the time-domain main body signal Acorresponding to each time-domain symbol that are used for filling thefrequency-domain subcarriers without phase modulation. If thetransmitting end has a PN modulation operation, here it refers to allpossible frequency-domain sequences after PN modulation.

When the set of known frequency-domain signalling of the symbol has onlyone known sequence, i.e. signalling is transmitted by only relying on afrequency-domain modulation frequency offset, the parsing method in thereceiving method in example I of signalling parsing can be simplified asfollows:

performing an FFT operation on the time-domain main body signal Acorresponding to each time-domain symbol, to obtain a frequency-domainsignal; taking out the value of valid subcarriers in thefrequency-domain signal; performing some calculation (a conjugatemultiplication/division calculation) on each valid subcarrier with avalid subcarrier of the unique known frequency-domain sequencecorresponding to the symbol, and conducting an IFFT calculation; basedon an IFFT result, optionally performing predefined processing; and thenusing a processed IFFT result between a plurality of symbols to furtherconduct a predefined processing operation between time-domain symbols toresolve the transmitted signalling (signalling conveyed using thefrequency-domain modulation offset, i.e. the time-domain cyclic shiftvalue).

Specifically, for some time-domain symbol, the expression of thepre-generated subcarrier without phase modulation corresponding to thetime-domain main body signal A thereof is A_(k), and the expressionthereof after phase modulation is

$\begin{matrix}{{{AM}_{k} = {A_{k} \cdot e^{j\frac{2\pi \; {sk}}{N_{FFT}}}}},} & \left( {{Formula}\mspace{14mu} 63} \right)\end{matrix}$

where H_(k) is a channel frequency-domain response, and after passingthrough a channel, the expression of received frequency-domain data is

$\begin{matrix}{{R_{k} = {{{{AM}_{k} \cdot H_{k}} + N_{k}} = {{A_{k} \cdot H_{k} \cdot e^{j\frac{2\pi \; {sk}}{N_{FFT}}}} + N_{k}}}},{k = 0},1,{{\ldots \mspace{14mu} N_{FFT}} - 1}} & \left( {{Formula}\mspace{14mu} 64} \right)\end{matrix}$

The predefined mathematical calculation (a conjugatemultiplication/division calculation) adnnted in this embodiment iscarried out,

$\begin{matrix}{{{E(t)}_{k} = {{\frac{R_{k}}{{A(t)}_{k}}\mspace{14mu} {or}\mspace{14mu} E_{k}} = {R_{k} \cdot \left( {A(i)}_{k} \right)^{*}}}},} & \left( {{Formula}\mspace{14mu} 65} \right)\end{matrix}$

where A(t)_(k) indicates the ^(t)th known sequence of the set of knownfrequency-domain sequence of the time-domain symbol, and t=1, . . . T,assuming that there are T sequences in total.

If the set of known frequency-domain sequences has only one knownsequence, i.e. T=1, then A(1)_(k)=A_(k). For example, when using thepredefined mathematical calculation method of

${E(t)}_{k} = \frac{R_{k}}{{A(t)}_{k}}$

division, if the set of known frequency-domain sequences comprises onlyone known sequence, then it is derived out that

$\begin{matrix}{{{E(1)}_{k} = {\frac{R_{k}}{{A(1)}_{k}} = {{H_{k} \cdot e^{j\frac{2\pi \; {sk}}{N_{FFT}}}} + \frac{N_{K}}{A_{k}}}}},} & \left( {{Formula}\mspace{14mu} 66} \right)\end{matrix}$

The physical meaning thereof is the product of the channel estimationvalue and phase modulation value of each subcarrier; and the formula forother predefined mathematical calculation

$\begin{matrix}{{{E(1)}_{k} = {{R_{k} \cdot \left( {A(1)}_{k} \right)^{*}} = {{{H_{k} \cdot {A_{k}}^{2}}e^{j\frac{2\pi \; {sk}}{N_{FFT}}}} + {N_{k} \cdot A_{k}^{*}}}}},} & \left( {{Formula}\mspace{14mu} 67} \right)\end{matrix}$

also contains the product of the channel estimation value and phasemodulation value of each subcarrier.

Then an IFFT operation is conducted on E(t)_(k), k=0,1, . . . N_(FFT)−1,then t IFFT operation results will be obtained for each time-domainsymbol; an absolute value calculation or square of absolute valueoperation is conducted on the results optionally; then the most reliableone in the T results in the case of t=1, . . . T is selected accordingto a first predefined selection rule as the calculation result of thetime-domain symbol; and the signalling conveyed by differentfrequency-domain sequences can be resolved using the ‘valuecorresponding thereto. The most reliable judgement method in the firstpredefined selection rule may be using the maximum peak or the maximumpeak-to-average ratio, etc.

If the set of known frequency-domain sequences of each time-domainsymbol includes only one known sequence, then the step of selecting themost reliable one in T results as the calculation result of the symbolcan be omitted, and the unique IFFT result of each symbol can bedirectly taken as the selected IFFT result.

FIG. 20 is an oscillograph of an inverse Fourier result of a time-domainmain body signal under AWGN in example I of signalling parsing of thepresent invention. As shown in FIG. 20, the position which the maximumvalue of the inverse discrete Fourier transform appears at is 1049, andthe value is 1.024.

Then assuming that the PFC part in the preamble symbol includes Qsymbols in total, the following wave form C(q), q=1, . . . Q of the Qsymbols will be obtained. Note that C(q) can be a result of someoriginal IFFT selected from T results, and can also be a result aftercalculating the absolute value or square of the absolute value.

Considering the influence of noise and multipath, and the influence ofan interference path under various reasons, for example, in the case of0 dB echo, 2 peaks will present, and it is difficult to judge themaximum peak. FIG. 21 provides an oscillograph of an inverse Fourierresult of a time-domain main body signal under an 0 dB echo channel inexample I of signalling parsing.

Therefore, as shown in FIG. 21, noise filtering processing is performedon the inverse Fourier calculation results of each time-domain symbol,i.e. keeping the maximum value and setting all the smaller values tozero. This step is optional. Processing results corresponding to all PFCsymbols are obtained, and are named as C′(q), _(q)=1, . . . Q

A schematic diagram of C′(q¹) and C′(q) of 2 symbols, i.e. a former oneand a later one, before and after processing under a 0 dB echo channelis provided below. FIG. 22(a) and FIG. 22(b) are respectively anoscillograph of an inverse Fourier result of a time-domain main bodysignal of a former time-domain signal and a later time-domain symbolbefore noise filter processing under an 0 dB echo channel in theembodiments; FIG. 23(a) and FIG. 23(b) are respectively an oscillographof an inverse Fourier result of a time-domain main body signal of aformer time-domain signal and a later time-domain symbol after noisefilter processing under an 0 dB echo channel in the embodiments.

The C′(q) of the later symbol is cyclically shifted, and is multipliedor conjugately multiplied by C′(q−1) of the former symbol and is thenaccumulated; the one corresponding to the maximum accumulated valueamong all the shift values is found out, and the transmitted signallingcan be derived from the shift value corresponding thereto; and after thepre-generated subcarrier is generated using the frequency-domainsequence of the time-domain main body signal A corresponding to thetime-domain symbol in the preamble symbol, the signalling transmissionfunction is realized by performing phase modulation on each validsubcarrier, which is equivalent to the way of performing cyclic shift onthe time-domain OFDM symbol after IFFT.

The particular description of the predefined processing operationbetween a plurality of time-domain symbols is as follows: cyclicallyshifting C′(q) by V to obtain C′(q,V), wherein left-wise shift orright-wise shift can be selected, and right-wise shift is selected inthis embodiment, V∈[0, N_(FFT)−1]; and then performing the conjugatemultiplication and accumulation calculation as the formula below forexample,

$\begin{matrix}{{{Accum}(V)} = {\sum\limits_{i = 0}^{N_{FFT} - 1}\; {{C^{\prime}\left( {q - 1} \right)} \cdot {{conj}\left( {C^{''}\left( {q,V} \right)} \right)}}}} & \left( {{Formula}\mspace{14mu} 68} \right)\end{matrix}$

It should be specially noted that the predefined processing operationbetween a plurality of time-domain symbols mentioned above is just anexample, and is not limited to conjugate multiplication; and themultiplication and accumulation operation therein do not have to beperformed on all N_(FFT) points, and can be performed at some greatvalue points.

Accum(V) with the maximum absolute value is finally selected, and thesignalling transmitted using a frequency-domain modulation frequencyoffset, i.e. a time-domain cyclic shift value, can be derived from thecorresponding V value thereto; the method of calculation is not limitedherein.

<Example II of Signalling Parsing>

In example II of signalling parsing, the steps of parsing signalling iscontained in the preamble symbol receiving method corresponding toexample I of signalling parsing, and the overall description of thepreamble symbol receiving method is omitted in example II of signallingparsing.

In the step S1-2 of determining the position of the preamble symbol in aphysical frame and parsing signalling information carried by thepreamble symbol, the signalling parsing step contains the followingparticular steps:

performing Fourier transform on the time-domain main body signal of eachof the time-domain symbol to extract valid subcarriers;

performing a predefined mathematical calculation on each of the validsubcarriers with the known subcarrier corresponding to each knownfrequency-domain sequence in a set of known frequency-domain signallingof the time-domain symbol and the channel estimation value, and thenperforming inverse Fourier transform, and obtaining a correspondinginverse Fourier result for each of the known frequency-domain sequence;and

each of the time-domain symbol selecting an inverse Fourier selectionresult from one or more of the inverse Fourier results according to afirst predefined selection rule, for directly resolving signallinginformation or performing a predefined processing operation between aplurality of the time-domain symbols, and resolving the signallinginformation based on an obtained inter-symbol processing result.

In this example II of signalling parsing: performing an FFT operation onthe time-domain main body signal A corresponding to each time-domainsymbol, to obtain a frequency-domain signal; taking out the value ofvalid subcarriers in the frequency-domain signal; after performing apredefined mathematical calculation (a conjugate multiplication/divisioncalculation) on each valid subcarrier with a known valid subcarriercorresponding to each known frequency-domain sequence of the set ofknown frequency-domain signalling of the symbol and a channel estimationvalue, conducting IFFT calculation, wherein each known frequency-domainsequence corresponds to one IFFT result, and each symbol corresponds toone or more IFFT results; selecting the most reliable selected IFFTresult of each symbol according to the predefined selection rule, andoptionally performing predefined processing. A signalling transmissionvalue can be directly obtained based on a selected IFFT result, and itis also possible to further use a processing results between a pluralityof symbols to conduct a predefined processing operation (e.g. delayedcorrelation) again between time-domain symbols to resolve thetransmitted signalling (including signalling conveyed using differentfrequency-domain sequences and/or signalling conveyed transmitted usinga frequency-domain modulation frequency offset, i.e. a time-domaincyclic shift value).

The set of known frequency-domain signalling refers to all possiblesequences of the time-domain main body signal A corresponding to eachtime-domain symbol that are used for filling the frequency-domainsubcarriers without phase modulation. If the transmitting end has a PNmodulation operation, here it refers to all possible frequency-domainsequences after PN modulation.

When the set of known frequency-domain signalling of the symbol has onlyone known sequence, i.e. signalling is transmitted by only relying on afrequency-domain modulation frequency offset, example II of signallingparsing can be simplified as follows:

performing an FFT calculation on the time-domain main body signal Acorresponding to each time-domain symbol, to obtain a frequency-domainsignal; taking out the value of valid subcarriers in thefrequency-domain signal; performing a predefined mathematicalcalculation (a conjugate multiplication/division calculation) on eachvalid subcarrier with a known subcarrier signal corresponding to theunique known frequency-domain sequence corresponding to the time-domainsymbol and a channel estimation value, and conducting an IFFTcalculation; based on an IFFT result, and optionally performingpredefined processing. A signalling transmission value can be directlyobtained, and it is also possible to use a processing results between aplurality of symbols to further conduct delayed correlation to resolvethe transmitted signalling (signalling conveyed using thefrequency-domain modulation frequency offset, i.e. the time-domaincyclic shift value)

Specifically, for some time-domain symbol, the expression of the knownsent pre-generated frequency-domain subcarrier without phase modulationcorresponding to the time-domain main body signal A thereof is A_(k),and the expression thereof after phase modulation is

$\begin{matrix}{{{AM}_{k} = {A_{k} \cdot e^{j\frac{2\pi \; {sk}}{N_{FFT}}}}},} & \left( {{Formula}\mspace{14mu} 69} \right)\end{matrix}$

where H_(k) is a channel frequency-domain response, and after passingthrough a channel, the expression of received frequency-domain data is

$\begin{matrix}{{R_{k} = {{{{AM}_{k} \cdot H_{k}} + N_{k}} = {{A_{k} \cdot H_{k} \cdot e^{j\frac{2\pi \; {sk}}{N_{FFT}}}} + N_{k}}}},{k = 0},1,{{\ldots \mspace{14mu} N_{FFT}} - 1}} & \left( {{Formula}\mspace{14mu} 70} \right)\end{matrix}$

Then a predefined mathematical calculation (a divisioncalculation/conjugate multiplication) is conducted

$\begin{matrix}{{{E(t)}_{k} = {{\frac{R_{k}}{{A(t)}_{k} \cdot H_{{est},k}}\mspace{14mu} {or}\mspace{14mu} E_{k}} = {R_{k} \cdot \left( {{A(t)}_{k} \cdot H_{{est},k}} \right)^{*}}}},} & \left( {{Formula}\mspace{14mu} 71} \right)\end{matrix}$

where A(t)_(k) indicates the t th known sequence of the set of knownfrequency-domain sequences; and t=1, . . . T, there are T sequences intotal. If the set of known frequency-domain sequences has only one knownsequence, i.e. T=1, then A(l)_(k)=A_(k), where H_(est) is a channelestimation value.

For example, the predefined mathematical calculation adopts the methodof

${{E(t)}_{k} = \frac{R_{k}}{{A(t)}_{k} \cdot H_{{est},k}}},$

if the set of known frequency-domain sequences comprises only one knownsequence, and H_(est)=H,

then

$\begin{matrix}{{{E(1)}_{k} = {\frac{R_{k}}{{A(1)}_{k} \cdot H_{{est},k}} = {e^{j\frac{2\pi \; {sk}}{N_{FFT}}} + \frac{N_{K}}{A_{k} \cdot H_{{est},k}}}}},} & \left( {{Formula}\mspace{14mu} 72} \right)\end{matrix}$

the physical meaning thereof is a phase modulation value of eachsubcarrier. The predefined mathematical calculation adopts anotheroperation formula

$\begin{matrix}{{{E(1)}_{k} = {{R_{k} \cdot \left( {{A(1)}_{k} \cdot H_{{est},k}} \right)^{*}} \approx {{{{H_{k}}^{2} \cdot {A_{k}}^{2}}e^{j\frac{2\pi \; {sk}}{N_{FFT}}}} + {{N_{k} \cdot A_{k}^{*}}H_{{est},k}^{*}}}}},} & \left( {{Formula}\mspace{14mu} 73} \right)\end{matrix}$

which also contains the phase modulation value of each subcarrier.

Then an IFFT calculation is conducted on E(t)_(k), k=0, 1, . . .N_(FFT)−1 then IFFT calculation results will be obtained for eachtime-domain symbol; an absolute value calculation or square of absolutevalue operation is conducted on the results optionally; then the mostreliable one in the T results in the case of t=1, . . . T is selectedaccording to the predefined selection rule as the calculation result ofthe time-domain symbol; and the signalling conveyed by differentfrequency-domain sequences can be resolved by means the valuecorresponding thereto. The most reliable judgement method in thepredefined selection rule may be using the maximum peak or the maximumpeak-to-average ratio, etc.

If the set of known frequency-domain sequences of each time-domainsymbol includes only one known sequence, then the step of selecting theone with the maximum peak-average-ratio in T results as the calculationresult of the symbol can be omitted, and the unique IFFT result of eachsymbol can be directly taken.

FIG. 24 is an oscillograph of an inverse Fourier result of a time-domainmain body signal under AWGN in example II of signalling parsing of thepresent invention. As shown in the figure, the position which themaximum value of the inverse discrete Fourier transform appears at is633, and the value is 0.9996.

Then assuming that the time-domain part in the preamble symbol includesQ time-domain symbols in total, the following wave form C(q), q=1, . . .Q of the Q time-domain symbols will be obtained. Note that C(q) can be aresult of some original IFFT selected from T results, and can also be aresult after computing the absolute value or the square of absolutevalue.

At this time, since an operation in the frequency domain can eliminatethe influence from the channel, the time-domain cyclic shift value canbe derived by directly using the position where the absolute value peakis located in C(q), thus deriving the signalling transmitted using thefrequency-domain modulation frequency offset, i.e. the time-domaincyclic shift value, for example, the position corresponding to themaximum peak is 633. (The calculation method is not limited herein.)

However, considering the influence of noise and multipath, and theinfluence of an interference path under various reasons, noise filteringprocessing can also be further performed on the calculation result ofeach symbol, i.e. keeping the maximum value and setting all the smallervalues to zero. This step is optional. Processing results correspondingto all time-domain symbols are obtained, and are named as C′(q), q=1, .. . Q.

The C′(q) of the later symbol is cyclically shifted, and is multipliedor conjugately multiplied by C′(q−1) of the former symbol and is thenaccumulated; the one corresponding to the maximum accumulated value inall the shift values is found out, and the transmitted signalling can bederived out using the shift value corresponding thereto. After thepre-generated subcarrier is generated using the frequency-domainsequence of the time-domain main body signal A corresponding to thetime-domain symbol satisfying the above-mentioned predefinedtransmitting rule, the signalling transmission function is realized byperforming phase modulation on each valid subcarrier, which isequivalent to the way of performing cyclic shift on the time-domain OFDMsymbol after IFFT.

The particular description is as follows: cyclically shifting C′(q) by Vto obtain C′(q,V), wherein left-wise shift or right-wise shift can beselected, and right-wise shift is selected in this embodiment, V∈[0,N_(FFT)−1];

and then performing the conjugate multiplication and accumulationcalculation as the formula below for example,

$\begin{matrix}{{{Accum}(V)} = {\sum\limits_{i = 0}^{N_{FFT} - 1}\; {{C^{\prime}\left( {q - 1} \right)} \cdot {{conj}\left( {C^{''}\left( {q,V} \right)} \right)}}}} & \left( {{Formula}\mspace{14mu} 74} \right)\end{matrix}$

It should be specially noted that the above-mentioned is just anexample, and is not limited to conjugate multiplication; and themultiplication and accumulation operation therein do not have to beperformed on N_(FFT) points, and can be performed at some great valuepoints.

Accum(V) with the maximum absolute value is finally selected, and thecorresponding V value thereto corresponds to the transmitted signalling.

Note that a first time-domain symbol of a preamble symbol is generallyknown, and the channel estimation value H_(est), used in theintroduction above can be obtained by means oftime-domain/frequency-domain estimation of a known sequence, i.e.obtained by dividing a known frequency-domain sequence by a receivedfrequency-domain signal in the frequency domain. With regard to thechannel estimation of a subsequent symbol: when the decoding of theprevious symbol is achieved, if the decoding is correct, performingchannel estimation again in the time domain/frequency domain by usingthe previous decoded information as known information, and performingsome specific operation on it with a previous channel estimation resultto obtain a new channel estimation result, for use of channel estimationof the signalling parsing for the next symbol.

It should be specifically noted that, due to the specific mathematicalrelationship between the IFFT calculation and the FFT calculation, usingFFT to realize the IFFT calculation mentioned in the example I ofsignalling parsing and the example II of signalling parsing equivalentlyalso does not depart from the contents of the present invention.

In both the example I of signalling parsing and the example II ofsignalling parsing, coherent demodulation is adopted, and noise iseliminated in the time domain, thus having great robust performanceunder a multi-path channel and a low signal-to-noise ratio. Compared tothe direct differential method in the frequency domain using a formerand a later symbol in the background art, the present invention avoidsthe amplification of noise. Moreover, the relative shift of thecalculation structures between the former and the later symbols isfurther used, thus solving the problem of misjudgement in the occurrenceof inaccurate channel estimation an interference path due to variousreasons.

<Example III of Signalling Parsing>

In example III of signalling parsing of the present invention, the flowof parsing signalling in the preamble symbol receiving method iscontained in the same preamble symbol receiving method corresponding tothe above-mentioned example I of signalling parsing, and the overalldescription of the preamble symbol receiving method is omitted inexample III of signalling parsing.

In example III of signalling parsing, the step of determining theposition of the preamble symbol and parsing signalling informationcarried by the preamble symbol comprises the following steps:

extending the set of known frequency-domain signalling of eachtime-domain symbol to be an extended set of know frequency-domainsignalling.

performing Fourier transform of the time-domain main body signal of eachof the time-domain symbol to extract valid subcarriers;

performing predefined mathematical calculation using each of the validsubcarriers and the known subcarrier corresponding to each knownfrequency-domain sequence in the extended set of known frequency-domainsignalling and the channel estimation value, and then accumulating thecalculation values on all the valid subcarriers; and

selecting an accumulated value from a plurality of accumulated valuesaccording to a second predefined selection rule, using a knownfrequency-domain sequence of the extended set of known frequency-domainsignalling corresponding to the accumulated value to infer thesignalling which is transmitted by utilizing the frequency-domainmodulation frequency offset, i.e. the time-domain cyclic shift value,and inferring a corresponding known frequency-domain sequence in theoriginal set of known frequency-domain signalling before extension, soas to resolve signalling information transmitted by differentfrequency-domain sequences.

Specifically, first of all, the set of known frequency-domain signallingof each time-domain symbol is extended to be an extended set of knowfrequency-domain signalling. Then an FFT calculation is performed on thetime-domain main body signal A corresponding to each time-domain symbolin the preamble symbol, to obtain a frequency-domain signal, and takingthe frequency-domain signal from the value of the valid subcarrier; apredefined mathematical calculation (conjugate multiplication/divisioncalculation) is conducted on each of the valid subcarriers with thesubcarrier signal corresponding to each known frequency-domain sequencein the extended set of known frequency-domain signalling and the channelestimation value, and then the calculation values on all the subcarriersare accumulated to obtain an accumulated value. Finally, the mostreliable accumulated value is selected based on a plurality ofaccumulated values according to a second predefined selection rule; themodulation frequency offset value can be inferred using a knownfrequency-domain sequence of the extended set of known frequency-domainsignalling corresponding to the accumulated value, thus obtaining thesignalling transmitted using the frequency-domain modulation frequencyoffset, i.e. the time-domain cyclic shift; a corresponding knownfrequency-domain sequence in the original set of known frequency-domainsignalling before extension is inferred out at the same time, so as toresolve signalling transmitted by different frequency-domain sequences.

When the set of known frequency-domain signalling of the symbol which isnot extended has only one known sequence, i.e. signalling is transmittedby only relying on a frequency-domain modulation frequency offset,example III of signalling parsing is simplified as follows:

First of all, the unique known frequency-domain sequence of each symbolis extended to be an extended set of know frequency-domain signalling.Then an FFT calculation is performed on the time-domain main body signalA corresponding to each time-domain symbol, to obtain a frequency-domainsignal, and taking the frequency-domain signal from the value of thevalid subcarrier; performing a predefined calculation (conjugatemultiplication/division calculation) on each of the valid subcarrierswith the subcarrier corresponding to each known frequency-domainsequence in the extended set of known frequency-domain signalling andthe channel estimation value, and then accumulating the calculationvalues on all the subcarriers to obtain an accumulated value. Finally,the most reliable accumulated value is selected based on a plurality ofaccumulated values; the modulation frequency offset value can beinferred using a corresponding known frequency-domain sequence in theextended set of known frequency-domain signalling, thus obtaining thesignalling transmitted using the frequency-domain modulation frequencyoffset, i.e. the time-domain cyclic shift value.

The frequency-domain known signalling set herein refers to all possiblefrequency-domain sequences of the time-domain main body signal Acorresponding to each time-domain symbol that are used for filling thefrequency-domain subcarriers without phase modulation. If thetransmitting end has a PN modulation operation, here it refers to allpossible frequency-domain sequences after PN modulation.

The extended set of known frequency-domain signalling is obtained by:performing corresponding subcarrier phase modulation on each knownfrequency-domain sequence in the known frequency-domain signalling setaccording to all possible frequency offset values, and using allpossible S modulation frequency offset values thereof to generate Sknown sequences after frequency offsets modulation. By way of example,if the original set of known frequency-domain signalling include T knownfrequency-domain sequences I_(t′), L₂, . . . , L_(T), then L_(t,1),L_(t,2), . . . , L_(t,S) and the like would be obtained respectively foreach known frequency-domain sequence L_(t′) according to S modulationfrequency offset values. By way of example:

${L_{k,t,s} = {L_{k,t} \cdot e^{j\frac{2\pi \; {sk}}{N_{FFT}}}}},{k = 0},1,,{N_{FFT} - 1},$

where k corresponds to a subcarrier serial number, with the serialnumber of a zero subcarrier being 0. The number S of modulationfrequency offset values is multiplied by the number T of knownfrequency-domain sequences, then T known frequency-domain sequenceswould be extended to be T·S known frequency-domain sequences,constructing an extended set of known frequency-domain signalling.

When the set of known frequency-domain signalling of the symbol which isnot extended has only one known sequence, i.e. signalling is transmittedby only relying on a frequency-domain modulation frequency offset,namely, the time-domain cyclic shift value, i.e. T=1, then the extendedset contains S known frequency-domain sequences in total.

Specifically, for example, assuming K=0:N_(zc)−1, where N_(zc) is thenumber of valid subcarriers, H_(est,k) is a channel estimation valuecorresponding to the kth valid subcarrier, R_(k) is the value of the kthvalid subcarrier received, L_(k,t,s) is the kth value of the (t, s)thsequence in the extended set of known frequency-domain sequences;

then

$\begin{matrix}{{{corr}_{t,s} = {{Re}\left( {\sum\limits_{k = 0}^{N_{ZC} - 1}\; {R_{k}H_{{est},k}^{*}L_{k,t,s}^{*}}} \right)}}{t = {{{0\text{:}\mspace{14mu} T} - {1\mspace{31mu} s}} = {{0\text{:}\mspace{14mu} S} - 1}}}} & \left( {{Formula}\mspace{14mu} 75} \right) \\{{{corr}_{t,s} = {\left( {\sum\limits_{k = 0}^{N_{ZC} - 1}\; {R_{k}H_{{est},k}^{*}L_{k,t,s}^{*}}} \right)}}{t = {{{0\text{:}\mspace{14mu} T} - {1\mspace{31mu} s}} = {{0\text{:}\mspace{14mu} S} - 1}}}} & \left( {{Formula}\mspace{14mu} 76} \right)\end{matrix}$

where | | indicates the operation of calculating an absolute value.

Taking t and s corresponding to max(corr_(t,s)), the modulationfrequency offset value can be inferred using a known frequency-domainsequence corresponding to s in the extended set of knownfrequency-domain signalling, thus obtaining the signalling transmittedusing the frequency-domain modulation frequency offset, i.e. thetime-domain cyclic shift; a corresponding known frequency-domainsequence in the original set of known frequency-domain signalling beforeextension is inferred using t at the same time, so as to resolvesignalling transmitted by different frequency-domain sequences.

When the set of known frequency-domain signalling of the symbol which isnot extended has only one known sequence, i.e. signalling is transmittedby only relying on a frequency-domain modulation frequency offset,namely, the time-domain cyclic shift value, i.e. T=1, then the extendedset contains S known frequency-domain sequences in total. The modulationfrequency offset value can be inferred using a known frequency-domainsequence corresponding to s in the extended set of knownfrequency-domain signalling, thus obtaining the signalling transmittedusing the frequency-domain modulation frequency offset, i.e. thetime-domain cyclic shift.

Note that a PFC part in a first time-domain symbol is generally known;therefore, the channel estimation value H_(est) used in the introductionabove can be obtained by means of time-domain/frequency-domainestimation of a known sequence, i.e. obtained by dividing a knownfrequency-domain sequence by a received frequency-domain signal in thefrequency domain. With regard to the channel estimation of a subsequentsymbol: when the decoding of the previous symbol is achieved, if thedecoding is correct, performing channel estimation again in the timedomain/frequency domain by using the previous decoded information assending information, and performing some specific calculation on it witha previous channel estimation result to obtain a new channel estimationresult, for use of the signalling parsing for the next symbol.

This embodiment also provides a preamble symbol receiving device statedin the Content of the invention above; the preamble symbol receivingdevice correspond to the preamble symbol receiving method in theabove-mentioned embodiments; then all the structural and technicalfactors of the device can be derived from the receiving method, thus thedescription therefor will be omitted.

The present invention has been disclosed above with the preferredembodiments which, however, are not intended to limit the presentinvention, and any person skilled in the art could make possible changesand alterations to the technical solutions of the present inventionusing the disclosed method and technical contents described abovewithout departing from the spirit and scope of the present invention.Therefore, any simple alteration, equivalent change and modificationwhich are made to the above-mentioned embodiments in accordance with thetechnical substance of the present invention and without departing fromthe contents of the present invention, will fall within the scope ofprotection of the technical solutions of the present invention.

1. A preamble symbol receiving method, characterized by comprising the following steps: processing a received signal; judging whether the processed signal obtained contains the preamble symbol desired to be received; and if a judgement result is yes, determining the position of the preamble symbol and resolving signalling information carried by the preamble symbol, wherein the received preamble symbol comprises at least one time-domain symbol generated by a transmitting end using a free combination of any number of first three-segment structures and/or second three-segment structures according to a predefined generation rule, the first three-segment structure containing: a time-domain main body signal, a prefix generated based on the entirety or a portion of the time-domain main body signal, and a postfix generated based on the entirety or a portion of a partial time-domain main body signal, and the second three-segment structure containing: the time-domain main body signal, a prefix generated based on the entirety or a portion of the time-domain main body signal, and a hyper prefix generated based on the entirety or a portion of the partial time-domain main body signal.
 2. The preamble symbol receiving method of claim 1, characterized in that the steps of judging whether the processed signal obtained contains the preamble symbol desired to be received, and if a judgement result is yes, determining the position of the preamble symbol and resolving signalling information carried by the preamble symbol contain at least any one of the following steps: initial timing synchronization, integer frequency offset estimation, fine timing synchronization, channel estimation, decoding analysis and fractional frequency offset estimation.
 3. The preamble symbol receiving method of claim 1, characterized in that at least any one of the following is utilized to judge if the processed signal contains the preamble symbol desired to be received: an initial timing synchronization method, an integer frequency offset estimation method, a fine timing synchronization method, a channel estimation method, a decoding result analysis method and a fractional frequency offset estimation method.
 4. The preamble symbol receiving method of claim 2, characterized in that the position of the preamble symbol is preliminarily determined by means of initial timing synchronization, and it is judged, based on a result of the initial timing synchronization, whether the processed signal contains the preamble symbol containing the three-segment structure and desired to be received.
 5. The preamble symbol receiving method of claim 4, characterized in that the position of the preamble symbol is preliminarily determined by means of any one of the following initial timing synchronization methods, a first initial timing synchronization method, comprising: performing necessary inverse processing on the processed signal by utilizing a processing relationship between any two segments in a first predefined three-segment time-domain structure and/or a second predefined three-segment time-domain structure, and performing delayed moving autocorrelation to acquire basic accumulation correlation values; when the signal comprises at least two time-domain symbols with a three-segment structure, grouping the basic accumulation correlation values according to different delay lengths of the delayed moving autocorrelation, and performing at least one delay relationship match and/or phase adjustment between symbols in each group according to a specific assembling relationship of the at least two time-domain symbols, and then carrying out a mathematical calculation to obtain several final accumulation correlation values with regard to a certain delay length, and when there is only one time-domain symbol with a three-segment structure, the final accumulation correlation value is the basic accumulation correlation value; and after performing delay relationship match and/or a specific predefined mathematical calculation based on at least one of the final accumulation correlation values, using the result of the calculation for initial timing synchronization; a second initial timing synchronization method, comprising: when a time-domain main body signal in any three-segment structure in the preamble symbol contains a known signal, performing a differential operation on the time-domain main body signal in accordance with N predefined differential values, and also performing a differential operation on a time-domain signal corresponding to known information, then correlating the two to obtain N sets of differential correlated results corresponding to the N differential values on a one-to-one basis, and performing initial synchronization based on the N sets of differential correlated results to obtain processed values for preliminarily determining the position of the preamble symbol, where N≧1, wherein when the determination of the position of the preamble symbol is completed based on the first initial timing synchronization method and the second initial timing synchronization method, weighting the processed values obtained respectively, and completing initial timing synchronization using the weighted results.
 6. The preamble symbol receiving method of claim 5, characterized in that the first initial timing synchronization method comprises: when the signal comprises two time-domain symbols with a three-segment structure, grouping the basic accumulation correlation values according to different delay lengths of the delayed moving autocorrelation, and for each set, performing one delay relationship match and/or phase adjustment between symbols according to a assembling relationship specific to the two time-domain symbols, and then carrying out a mathematical calculation to obtain several final accumulation correlation values with a certain delay length.
 7. The preamble symbol receiving method of claim 6, characterized in that the first initial timing synchronization method further comprises adjusting, within a certain range, delay lengths that there should be during each delayed moving autocorrelation, to form a plurality of adjusted delay lengths; then performing delayed moving autocorrelation according to the plurality of obtained adjusted delay lengths and the delay lengths that there should be, and choosing a correlation result which is the most significant as the basic accumulation correlation value.
 8. The preamble symbol receiving method of claim 5, characterized in that the N differential values are selected according to at least any one of the following predefined differential selection rules, for initial synchronization: a first predefined differential selection rule containing: selecting any several differential values within the range of the length of a local time-domain sequence corresponding to the known information; and a second predefined differential selection rule contains: selecting several different values which constitute an arithmetic sequence, within the range of the length of a local temporal sequence corresponding to the known information.
 9. The preamble symbol receiving method of claim 8, characterized in that when the N differential values are selected by means of the first predefined differential selection rule, accumulating or averaging the weighted absolute values of N sets of differential correlated results obtained on a one-to-one basis; or when the N differential values are selected using the first predefined differential selection rule or the second predefined differential selection rule, accumulating or averaging weighted vectors of the obtained N sets of differential correlated results.
 10. The preamble symbol receiving method of claim 5, characterized in that fractional frequency offset estimation is conducted by utilizing a result of the first initial timing synchronization method and/or the second initial timing synchronization method, when a result of the first initial timing synchronization method is used, the result comprises the final accumulation correlation value obtained by performing predefined processing calculation utilizing a processing relationship corresponding to the time-domain main body signal and the prefix in the first three-segment structure and/or the second three-segment structure, and a second fractional frequency offset value is calculated from the accumulation correlation value; the result of the first initial timing synchronization method also comprises two said final accumulation correlation values obtained by performing predefined processing calculation utilizing a processing relationship corresponding to the time-domain main body signal and the postfix/the hyper prefix and a processing relationship corresponding to the prefix and the postfix/the hyper prefix in the first three-segment structure and/or the second three-segment structure, and a third fractional frequency offset value is calculated from the two accumulation correlation values; the fractional frequency offset estimation can be conducted based on at least any one of the obtained second fractional frequency offset value and third fractional frequency offset value; and when utilizing the results of the first initial timing synchronization method and the second initial timing synchronization method, a fractional frequency offset value is obtained based on at least any one of or a combination of at least any two of the first fractional frequency offset value, the second fractional frequency offset value and the third fractional frequency offset value.
 11. The preamble symbol receiving method of claim 2, characterized in that based on a result of the initial timing synchronization method, if it is detected that the result satisfies a pre-set condition, then it is determined that the processed signal contains an expected preamble symbol containing the three-segment structure, wherein the pre-set condition contains: conducting a specific calculation based on the result of the initial timing synchronization, and then judging whether the maximum value of a calculation result exceeds a predefined threshold, or further determining it in conjunction with an integer frequency offset estimation result and/or a decoding result.
 12. The preamble symbol receiving method of claim 2, characterized in that the preamble symbol receiving method further comprises: conducting fractional frequency offset estimation by utilizing a result of an initial timing synchronization method.
 13. The preamble symbol receiving method of claim 1, characterized in that the step of determining the position of the preamble symbol and resolving signalling information carried by the preamble symbol comprises: resolving signalling information carried by the preamble symbol by utilizing the entirety or a portion of a time-domain waveform of the preamble symbol and/or a frequency-domain signal obtained from the entirety or a portion of the time-domain waveform of the preamble symbol through Fourier transform.
 14. The preamble symbol receiving method of claim 1, characterized in that in the predefined generation rule, the generated preamble symbol comprises: a free combination of several time-domain symbols with the first three-segment structure and/or several time-domain symbols with the second three-segment structure arranged in any order, wherein the first three-segment structure containing: a time-domain main body signal, a prefix generated based on a rear part of the time-domain main body signal, and a postfix generated based on the rear part of the time-domain main body signal, and the second three-segment structure containing: a time-domain main body signal, a prefix generated based on a rear part of the time-domain main body signal, and a hyper prefix generated based on the rear part of the time-domain main body signal.
 15. The preamble symbol receiving method of claim 14, characterized in that when a transmitting end generates the postfix or the hyper prefix by truncating a partial signal from the time-domain main body signal, different start points of the truncation are used for transmitting different signalling information, and the signalling is parsed based on the following: different delay relationships of the same content between the prefix and the postfix or the hyper prefix, and/or the time-domain main body signal and the postfix or the hyper prefix.
 16. The preamble symbol receiving method of claim 15, characterized in that the parsed signalling contains emergency broadcast.
 17. The preamble symbol receiving method of claim 1, characterized in that the preamble symbol is obtained by processing a frequency-domain symbol, and the generation step of the frequency-domain symbol comprises: arranging a fixed sequence and a signalling sequence, which are generated respectively, in a predefined arrangement rule, and filling valid subcarrier with arranged fixed sequence and signalling sequence.
 18. The preamble symbol receiving method of claim 17, characterized in that the step of resolving signalling information carried by the preamble symbol comprises: resolving the signalling information carried by signalling sequence subcarriers in the preamble symbol by performing calculation using a signal containing all or some of the signalling sequence subcarriers and a set of signalling sequence subcarriers, or resolving the signalling information carried by the signalling sequence subcarriers in the preamble symbol by performing calculation using a time-domain signal corresponding to the entirety or a portion of the set of signalling sequence subcarriers.
 19. The preamble symbol receiving method of claim 17, characterized in that conducting fine timing synchronization using a fixed subcarrier sequence contained in at least one time-domain symbol.
 20. The preamble symbol receiving method of claim 2, characterized in that when the time-domain main body signal in the preamble symbol or a corresponding frequency-domain main body signal contains a known signal, the preamble symbol receiving method further comprises integer frequency offset estimation in any of the following manners: according to a result of the initial timing synchronization, truncating a section of time-domain signal at least containing the entirety or a portion of the time-domain main body signal, modulating the truncated section of time-domain signal using different frequency offsets in a frequency sweeping manner to obtain N frequency sweeping time-domain signals corresponding to the offset values on a one-to-one basis, and after performing moving correlation between a known time-domain signal obtained by performing inverse Fourier transform on a known frequency-domain sequence and each frequency sweeping time-domain signal, comparing the maximum correlation peaks of N correlation results, regarding a frequency offset value by which a frequency sweeping time-domain signal corresponding to the maximum correlation result is modulated as the integer frequency offset estimation value; or performing Fourier transform on the time-domain signal which is truncated to the length of the time-domain main body signal according to the result of the initial timing synchronization, conducting cyclic shift on the obtained frequency-domain subcarriers using different shift values within a frequency sweeping range, truncating a received sequence corresponding to a valid subcarrier, performing predefined calculation and then inverse transform on the received sequence and the known frequency-domain sequence, performing selection from several groups of inverse transform results corresponding to the shift values on a one-to-one basis to obtain a corresponding shift value, and obtaining the integer frequency offset estimation value according to a corresponding relationship between the shift value and the integer frequency offset estimation value.
 21. The preamble symbol receiving method of claim 2, characterized in that the step of channel estimation comprises: performing arbitrarily on the time domain and/or on the frequency domain: after finishing the decoding of the previous time-domain main body signal, using obtained decoded information as known information to perform channel estimation on the time domain/frequency domain once again and perform certain specific calculation with a previous channel estimation result to obtain a new channel estimation result, which will be used in channel estimation of signalling parsing for the next time-domain main body signal.
 22. The preamble symbol receiving method of claim 1, characterized in that the received preamble symbol is obtained by processing the frequency-domain subcarriers, the frequency-domain subcarriers being generated based on the frequency-domain main body sequence, the steps of generating the frequency-domain subcarriers contain: a predefined sequence generation rule for generating the frequency-domain main body sequence, and/or a predefined processing rule for processing the frequency-domain main body sequence to generate the frequency-domain subcarriers; the predefined sequence generation rule contains either one of or a combination of two of the following: generating a sequence based on different sequence generation formulas; and/or generating a sequence based on the same sequence generation formula, and further preforming cyclic shift on the generated sequence. the predefined processing rule contains: according to the frequency offset value, performing phase modulation on a pre-generated subcarrier which is obtained by processing the frequency-domain main body sequence.
 23. The preamble symbol receiving method of claim 22, characterized in that when the preamble symbol at least contains one time-domain symbol, in the case where a first time-domain symbol contains known information, fine timing synchronization is conducted by utilizing the known information.
 24. The preamble symbol receiving method of claim 22, characterized in that in the step of parsing signalling information, firstly, producing a set of known signalling sequences using all possible different root values and/or different frequency-domain shift values, and then conducting calculation using the set of signalling sequences and all possible frequency-domain modulation frequency offset values and a frequency-domain main body sequence sent by the transmitting end.
 25. The preamble symbol receiving method of claim 22, characterized in that when the time-domain main body signal in the preamble symbol or a corresponding frequency-domain main body signal contains a known signal, the preamble symbol receiving method further comprises integer frequency offset estimation in any of the following manners: according to a result of the initial timing synchronization, truncating a section of time-domain signal at least containing the entirety or a portion of the time-domain main body signal, modulating the truncated section of time-domain signal using different frequency offsets in a frequency sweeping manner to obtain N frequency sweeping time-domain signals corresponding to the offset values on a one-to-one basis, and after performing moving correlation between a known time-domain signal obtained by performing inverse Fourier transform on a known frequency-domain sequence and each frequency sweeping time-domain signal, comparing the maximum correlation peaks of N correlation results, regarding a frequency offset value by which a frequency sweeping time-domain signal corresponding to the maximum correlation result is modulated as the integer frequency offset estimation value; or performing Fourier transform on the time-domain signal which is truncated to the length of the time-domain main body signal according to the result of the initial timing synchronization, conducting cyclic shift on the obtained frequency-domain subcarriers using different shift values within a frequency sweeping range, truncating a received sequence corresponding to a valid subcarrier, performing predefined calculation and then inverse transform on the received sequence and the known frequency-domain sequence, performing selection from several groups of inverse transform results corresponding to several groups of shift values on a one-to-one basis to obtain a corresponding shift value, and obtaining the integer frequency offset estimation value according to a corresponding relationship between the shift value and the integer frequency offset estimation value.
 26. The preamble symbol receiving method of claim 22, characterized in that the step of channel estimation comprises: performing arbitrarily on the time domain and/or on the frequency domain: after finishing the decoding of the previous time-domain main body signal, using obtained decoded information as known information to perform channel estimation on the time domain/frequency domain once again and perform certain specific calculation with a previous channel estimation result to obtain a new channel estimation result, which will be used in channel estimation of signalling parsing for the next time-domain main body signal.
 27. The preamble symbol receiving method of claim 25, characterized in that after the integer frequency offset estimation, compensating the frequency offset and parsing the transmitted signalling.
 28. The preamble symbol receiving method of claim 22, characterized in that when generating a sequence using different sequence generation formulas; and/or generating a sequence based on the same sequence generation formula, and further preforming cyclic shift on the generated sequence, in the process of generating the frequency-domain subcarrier, performing a specific mathematical calculation on the frequency-domain signalling subcarriers and the channel estimation result, and all possible frequency-domain main body sequences, so as to parse the signalling, wherein the specific mathematical calculation contains any one of the following: maximum likelihood correlation calculation incorporating channel estimation; or performing channel equalization on the frequency-domain signalling subcarrier using the channel estimation value, then performing correlation calculation with all of the possible frequency-domain main body sequences, and selecting the maximum correlation value as a decoding result of signalling parsing.
 29. The preamble symbol receiving method of claim 22, characterized in that the process of generating the frequency-domain subcarrier includes: performing phase modulation on a pre-generated subcarrier using the frequency offset value, or performing cyclic shift in the time domain after inverse Fourier transform.
 30. The preamble symbol receiving method of claim 29, characterized in that the step of determining the position of the preamble symbol and parsing signalling information carried by the preamble symbol comprises: performing Fourier transform of the time-domain main body signal of each of the time-domain symbol to extract valid subcarriers; performing predefined mathematical calculation using each of the valid subcarriers and a known subcarrier signal corresponding to each known frequency-domain sequence in a set of known frequency-domain signalling of the time-domain symbol, and a channel estimation result and then performing inverse Fourier transform, and obtaining a corresponding inverse Fourier result for each of the known frequency-domain sequence; and each of the time-domain symbol selecting an inverse Fourier selection result from one or more of the inverse Fourier results according to a first predefined selection rule, then performing a predefined processing operation using a plurality of the time-domain symbols, and resolving the signalling information based on an obtained inter-symbol processing result.
 31. The preamble symbol receiving method of claim 30, characterized in that calculating the absolute value or square of the absolute value of the inverse Fourier selection result, and then selecting the inverse Fourier selection result according to the first predefined selection rule.
 32. The preamble symbol receiving method of claim 31, characterized in that the first predefined selection rule contains performing selection according to the maximum peak value and/or performing selection according to the peak-to-average ratio.
 33. The preamble symbol receiving method of claim 30, characterized in that the method further comprises: a noise filtering processing step comprising: noise filtering processing can be performed on the inverse Fourier result of each time-domain symbol, with large values being reserved and all smaller values being set to zero.
 34. The preamble symbol receiving method of claim 30, characterized in that the parsed signalling information contains: signalling transmitted using different frequency-domain sequences and/or signalling transmitted using a frequency-domain modulation frequency offset, i.e. a time-domain cyclic shift value.
 35. The preamble symbol receiving method of claim 30, characterized in that the set of known frequency-domain signalling refers to all possible frequency-domain sequences of the time-domain main body signal corresponding to each time-domain symbol on frequency-domain subcarriers while phase modulation is not performed.
 36. The preamble symbol receiving method of claim 30, characterized in that if there is only one known sequence within a set of known frequency-domain sequences of the time-domain symbols, the first predefined selection rule is: directly selecting the unique inverse Fourier result of each of the time-domain symbols as the inverse Fourier selection result, then performing a predefined processing operation between a plurality of the time-domain symbols, and resolving the signalling information based on an obtained inter-symbol processing result.
 37. The preamble symbol receiving method of claim 30, characterized in that the predefined mathematical calculation contains: conjugate multiplication or division calculation.
 38. The preamble symbol receiving method of claim 30, characterized in that the step of performing a predefined processing operation between a plurality of the time-domain symbols and resolving the signalling information based on an obtained inter-symbol processing result comprises: multiplying or conjugate multiplying a later time-domain symbol which have been cyclically shifted and a former time-domain symbol, and accumulating to obtain an accumulated value, finding out a shift value corresponding to a maximum accumulated value among all the predefined frequency offset values or cyclic shift values, and deriving the signalling information from the shift value.
 39. The preamble symbol receiving method of claim 29, characterized in that the method comprises: the step of determining the position of the preamble symbol and parsing signalling information carried by the preamble symbol comprises: extending the set of known frequency-domain signalling of each time-domain symbol to be an extended set of know frequency-domain signalling; performing Fourier transform of the time-domain main body signal of each of the time-domain symbol to extract valid subcarriers; performing predefined mathematical calculation using each of the valid subcarriers and a known subcarrier signal corresponding to each known frequency-domain sequence in the extended set of known frequency-domain signalling and a channel estimation value, and then accumulating the calculation values on all the valid subcarriers; and selecting an accumulated value from a plurality of accumulated values according to a second predefined selection rule, using a known frequency-domain sequence of the extended set of known frequency-domain signalling corresponding to the accumulated value to infer the signalling transmitted using the frequency-domain modulation frequency offset value, i.e. the time-domain cyclic shift, and selecting a corresponding known frequency-domain sequence from the original set of known frequency-domain signalling before extension, so as to resolve signalling information transmitted by different frequency-domain sequences.
 40. The preamble symbol receiving method of claim 39, characterized in that the second predefined selection rule contains performing selection according to the maximum absolute value or performing selection according to the maximum real part.
 41. The preamble symbol receiving method of claim 39, characterized in that the set of known frequency-domain signalling refers to all possible frequency-domain sequences of the time-domain main body signal corresponding to each time-domain symbol that are used for filling the frequency-domain subcarriers while phase modulation is not performed.
 42. The preamble symbol receiving method of claim 39, characterized in that the extended set of known frequency-domain signalling is obtained in the following way: performing phase modulation on each known frequency-domain sequence of the set of known frequency-domain signalling on the subcarriers using all possible frequency offset values, wherein all the possible S modulation frequency offset values correspondingly generate S frequency offset modulated known sequences.
 43. The preamble symbol receiving method of claim 42, characterized in that when there is only one known sequence within the non-extended set of known frequency-domain signalling of the symbol, namely, the signalling information is transmitted only by a frequency-domain modulation frequency offset s, i.e., the time-domain cyclic shift value, the extended set of known frequency-domain signalling contains altogether S known frequency-domain sequences, and the modulation frequency offset value can be inferred by utilizing the known frequency-domain sequences of the extended set of known frequency-domain signalling corresponding to the modulation frequency offset s, thus obtaining the signalling information transmitted by the frequency-domain modulation frequency offset, i.e. the time-domain cyclic shift.
 44. The preamble symbol receiving method of claim 39, characterized in that the predefined mathematical calculation contains: conjugate multiplication or division calculation.
 45. The preamble symbol receiving method of claim 29, characterized in that the step of determining the position of the preamble symbol and parsing signalling information carried by the preamble symbol comprises: performing Fourier transform on the time-domain main body signal of each of the time-domain symbol to extract valid subcarriers; performing a predefined mathematical calculation using each of the valid subcarriers and a known subcarrier signal corresponding to each known frequency-domain sequence in a set of known frequency-domain signalling of the time-domain symbol and a channel estimation value, and then performing inverse Fourier transform, and obtaining a corresponding inverse Fourier result for each of the known frequency-domain sequence; and each of the time-domain symbol, based on an inverse Fourier selection result selected from one or more of the inverse Fourier results according to a first predefined selection rule, performing a predefined processing operation using a plurality of the time-domain symbols, and resolving the signalling information based on an obtained inter-symbol processing result.
 46. The preamble symbol receiving method of claim 45, characterized in that the method further comprises: calculating the absolute value or the square of the absolute value of the inverse Fourier selection result, and then selecting the inverse Fourier selection result according to the first predefined selection rule.
 47. The preamble symbol receiving method of claim 45, characterized in that the first predefined selection rule contains performing selection according to the maximum peak value and/or performing selection according to the peak-to-average ratio.
 48. The preamble symbol receiving method of claim 45, characterized in that the method further comprises: a noise filtering processing step comprising: noise filtering processing can be performed on the inverse Fourier result of each time-domain symbol, with large values being reserved and all smaller values being set to zero.
 49. The preamble symbol receiving method of claim 45, characterized in that the parsed signalling information contains: signalling transmitted using different frequency-domain sequences and/or signalling transmitted using a frequency-domain modulation frequency offset, i.e. a time-domain cyclic shift value.
 50. The preamble symbol receiving method of claim 45, characterized in that the set of known frequency-domain signalling refers to all possible sequences of the time-domain main body signal corresponding to each time-domain symbol that are used for filling the frequency-domain sequence of the subcarriers before performing phase modulation on of the frequency-domain subcarriers.
 51. The preamble symbol receiving method of claim 45, characterized in that if there is only one known sequence within a set of known frequency-domain sequences of the time-domain symbols, the first predefined selection rule is: directly selecting the unique inverse Fourier result of each of the time-domain symbols as the inverse Fourier selection result, then performing a predefined processing operation between a plurality of the time-domain symbols, and resolving the signalling information based on an obtained inter-symbol processing result.
 52. The preamble symbol receiving method of claim 45, characterized in that the predefined mathematical calculation contains: conjugate multiplication or division calculation.
 53. The preamble symbol receiving method of claim 45, characterized in that the step of performing a predefined processing operation on a plurality of the time-domain symbols, and resolving the signalling information based on an obtained inter-symbol processing result comprises: multiplying or conjugate multiplying a later time-domain symbol which have been cyclically shifted and a former time-domain symbol, and accumulating to obtain an accumulated value, finding out a shift value corresponding to a maximum accumulated value in all the predefined frequency offset values or cyclic shift values, and deriving the signalling information from the shift value.
 54. A preamble symbol receiving method, characterized by comprising the following steps: processing a received signal; judging whether the processed signal obtained contains the preamble symbol desired to be received; and if a judgement result is yes, determining the position of the preamble symbol and resolving signalling information carried by the preamble symbol, wherein the received preamble symbol is obtained by processing a frequency-domain symbol, and the generation step of the frequency-domain symbol comprises: arranging a fixed sequence and a signalling sequence, which are generated respectively, in a predefined arrangement rule, and filling the arranged fixed sequence and signalling sequence onto a valid subcarrier.
 55. The preamble symbol receiving method of claim 54, characterized in that at least one of the following methods is utilized to judge if the processed signal contains the preamble symbol desired to be received: an initial timing synchronization method, an integer frequency offset estimation method, a fine timing synchronization method, a channel estimation method, a decoding result analysis method and a fractional frequency offset estimation method.
 56. The preamble symbol receiving method of claim 54, characterized in that the functions of judging if the received signal, which has been processed, contains the preamble symbol desired to be received, and if a judgement result is yes, determining the position of the preamble symbol and resolving signalling information carried by the preamble symbol contains are realized by utilizing at least any one of the following steps: initial timing synchronization, integer frequency offset estimation, fine timing synchronization, channel estimation, decoding analysis and fractional frequency offset estimation.
 57. The preamble symbol receiving method of claim 54, characterized in that using the fixed sequence to perform an integer frequency offset estimation or channel estimation comprises the following steps: according to the determined position of the preamble symbol, truncating a signal containing the entirety or a portion of the fixed subcarrier; and performing calculation using the truncated signal and a frequency-domain fixed subcarrier sequence or a time-domain signal corresponding to the frequency-domain fixed subcarrier sequence, so as to realize an integer frequency offset estimation or channel estimation.
 58. The preamble symbol receiving method of claim 54, characterized in that conducting fine timing synchronization using a fixed subcarrier sequence contained in at least one time-domain symbol in the preamble symbol.
 59. The preamble symbol receiving method of claim 54, characterized in that the step of determining the position of the preamble symbol and resolving signalling information carried by the preamble symbol comprises: resolving the signalling information carried by the preamble symbol by utilizing the entirety or a portion of a time-domain waveform of the preamble symbol and/or a frequency-domain signal obtained through performing Fourier transform on the entirety or a portion of the time-domain waveform of the preamble symbol.
 60. The preamble symbol receiving method of claim 54, characterized in that the method further comprises: when the time-domain main body signal in the preamble symbol or a corresponding frequency-domain main body signal contains a known signal, the method further comprises performing any of the following integer frequency offset estimation using the preamble symbol: according to a result of the initial timing synchronization, truncating a section of time-domain signal at least containing the entirety or a portion of the time-domain main body signal, modulating the truncated section of time-domain signal using different frequency offsets in a frequency sweeping manner to obtain N frequency sweeping time-domain signals corresponding to the offset values on a one-to-one basis, and after performing moving correlation between a known time-domain signal obtained by performing inverse transform on a known frequency-domain sequence and each frequency sweeping time-domain signal, comparing the maximum correlation peaks of N correlation results, regarding a frequency offset value by which a frequency sweeping time-domain signal corresponding to the maximum correlation result is modulated as the integer frequency offset estimation value; or performing Fourier transform on the time-domain signal which is truncated to the length of the time-domain main body signal using the result of the initial timing synchronization, conducting cyclic shift on the obtained frequency-domain subcarriers using different shift values within a frequency sweeping range, truncating a received sequence corresponding to a valid subcarrier, performing predefined calculation and then inverse Fourier transform on the received sequence and the known frequency-domain sequence, performing selection from several groups of inverse transform results corresponding to the shift values on a one-to-one basis to obtain a corresponding shift value, and obtaining the integer frequency offset estimation value according to a corresponding relationship between the shift value and the integer frequency offset estimation value.
 61. The preamble symbol receiving method of claim 54, characterized in that the step of resolving signalling information carried by the preamble symbol comprises: resolving the signalling information carried by signalling sequence subcarriers in the preamble symbol by performing calculation using a signal containing all or some of the signalling sequence subcarriers and a set of signalling sequence subcarriers, or a time-domain signal corresponding to the set of signalling sequence subcarriers.
 62. A preamble symbol receiving method, characterized by comprising the following steps: processing a received signal; judging whether the received signal, which has been processed, contains the preamble symbol desired to be received; and if a judgement result is yes, determining the position of the preamble symbol and resolving signalling information carried by the preamble symbol, the received preamble symbol is obtained by performing inverse Fourier transform on the frequency-domain subcarrier, the frequency-domain subcarrier being generated based on the frequency-domain main body sequence, the steps of generating the frequency-domain subcarrier contains: a predefined sequence generation rule for generating the frequency-domain main body sequence, and/or a predefined processing rule for processing the frequency-domain main body sequence to generate the frequency-domain subcarrier; the predefined sequence generation rule contains either one of or a combination of two of the following: generating a sequence based on different sequence generation formulas; and/or generating a sequence based on the same sequence generation formula, and further preforming cyclic shift on the generated sequence. the predefined processing rule contains: according to the predefined frequency offset value, performing phase modulation on a pre-generated subcarrier which is obtained by processing the frequency-domain main body sequence.
 63. The preamble symbol receiving method of claim 62, characterized in that the steps of judging whether the processed signal obtained contains the preamble symbol desired to be received, and if a judgement result is yes, determining the position of the preamble symbol and resolving signalling information carried by the preamble symbol contain at least any one of the following steps: initial timing synchronization, integer frequency offset estimation, fine timing synchronization, channel estimation, decoding analysis and fractional frequency offset estimation.
 64. The preamble symbol receiving method of claim 62, characterized in that at least any one of the following method is utilized to judge if the processed signal contains the preamble symbol desired to be received: an initial timing synchronization method, an integer frequency offset estimation method, a fine timing synchronization method, a channel estimation method, a decoding result analysis method and a fractional frequency offset estimation method.
 65. The preamble symbol receiving method of claim 63, characterized in that when the preamble symbol contains at least one time-domain symbol, if a first time-domain symbol contains known information, fine timing synchronization is conducted by utilizing the known information.
 66. The preamble symbol receiving method of claim 63, characterized in that the step of channel estimation comprises: performing arbitrarily on the time domain and/or on the frequency domain: after finishing the decoding of the previous time-domain main body signal, using obtained decoded information as transmitting information to perform channel estimation on the time domain/frequency domain once again and perform certain specific calculation with a previous channel estimation result to obtain a new channel estimation result, which will be used in channel estimation of signalling parsing for the next time-domain main body signal.
 67. The preamble symbol receiving method of claim 63, characterized in that when the time-domain main body signal in the preamble symbol or a corresponding frequency-domain main body signal contains a known signal, the preamble symbol receiving method further comprises integer frequency offset estimation in any of the following manners: modulating the entirety or a portion of the truncated time-domain signal using different frequency offsets in a frequency sweeping manner to obtain several frequency sweeping time-domain signals, and after performing moving correlation between a known time-domain signal obtained by performing inverse transform on a known frequency-domain sequence and each frequency sweeping time-domain signal, regarding a frequency offset value by which a frequency sweeping time-domain signal of the maximum correlation peak value is modulated as the integer frequency offset estimation value; or conducting cyclic shift on frequency-domain subcarriers, which are obtained by performing Fourier transform on the time-domain main body signal truncated according to the position result of the initial timing synchronization, using different shift values within a frequency sweeping range, truncating a received sequence corresponding to a valid subcarrier, performing predefined calculation and then inverse transform on the received sequence and the known frequency-domain sequence, obtaining a shift value by means of selection from inverse transform results corresponding to several groups of shift values, thereby obtaining the integer frequency offset estimation value using a corresponding relationship between the shift value and the integer frequency offset estimation value.
 68. The preamble symbol receiving method of claim 62, characterized in that after the integer frequency offset estimation, compensating the frequency offset and parsing the transmitted signalling.
 69. The preamble symbol receiving method of claim 62, characterized in that when generating a sequence using different sequence generation formulas; and/or generating a sequence based on the same sequence generation formula, and further preforming cyclic shift on the generated sequence, in the process of generating the frequency-domain subcarrier, performing a specific mathematical calculation on the frequency-domain signalling subcarrier and the channel estimation value, and all possible frequency-domain main body sequence, so as to parse the signalling, wherein the specific mathematical calculation contains any one of the following: maximum likelihood correlation calculation incorporating channel estimation; or performing channel equalization on the frequency-domain signalling subcarrier using the channel estimation value, then performing correlation calculation using an equalized signal and all of the possible frequency-domain main body sequences, and selecting the maximum correlation value as a decoding result of signalling parsing.
 70. The preamble symbol receiving method of claim 62, characterized in that the step of determining the position of the preamble symbol and resolving signalling information carried by the preamble symbol comprises: resolving the signalling information carried by the preamble symbol by utilizing the entirety or a portion of a time-domain waveform of the preamble symbol and/or utilizing a frequency-domain signal obtained through performing Fourier transform on the entirety or a portion of the time-domain waveform of the preamble symbol.
 71. The preamble symbol receiving method of claim 62, characterized in that the generation process of the frequency-domain subcarrier includes: performing phase modulation on a pre-generated subcarrier using the frequency offset value or performing inverse Fourier transform on the frequency-domain subcarriers and then performing cyclic shift in the time domain.
 72. The preamble symbol receiving method of claim 71, characterized in that the step of determining the position of the preamble symbol and parsing signalling information carried by the preamble symbol comprises: performing Fourier transform on the time-domain main body signal of each of the time-domain symbol to extract valid subcarriers; performing predefined mathematical calculation using each of the valid subcarriers and a known subcarrier corresponding to each known frequency-domain sequence in a set of known frequency-domain signalling of the time-domain symbol and a channel estimation value, and then performing inverse Fourier transform, and obtaining a corresponding inverse Fourier transform result for each of the known frequency-domain sequence; and each of the time-domain symbol, based on an inverse Fourier selection result selected from one or more of the inverse Fourier results according to a first predefined selection rule, performing a predefined processing operation on a plurality of the time-domain symbols, and resolving the signalling information based on an obtained inter-symbol processing result.
 73. The preamble symbol receiving method of claim 72, characterized in that the method further comprises: calculating the absolute value or square of the absolute value of the inverse Fourier selection result, and then selecting the inverse Fourier selection result according to the first predefined selection rule.
 74. The preamble symbol receiving method of claim 72, characterized in that the first predefined selection rule contains performing selection according to the maximum peak value and/or performing selection according to the peak-to-average ratio.
 75. The preamble symbol receiving method of claim 72, characterized in that the method further comprises: a noise filtering processing step comprising: noise filtering processing can be performed on the inverse Fourier result of each time-domain symbol, with large values being reserved and all smaller values being set to zero.
 76. The preamble symbol receiving method of claim 72, characterized in that the parsed signalling information contains: signalling transmitted using different frequency-domain sequences and/or signalling transmitted using a frequency-domain modulation frequency offset, i.e. a time-domain cyclic shift value.
 77. The preamble symbol receiving method of claim 72, characterized in that the set of known frequency-domain signalling refers to all possible frequency-domain sequences of the time-domain main body signal corresponding to each time-domain symbol that are used for filling the frequency-domain subcarriers while phase modulation is not performed.
 78. The preamble symbol receiving method of claim 72, characterized in that if there is only one known sequence within a set of known frequency-domain sequences of the time-domain symbols, the first predefined selection rule is: directly selecting the unique inverse Fourier result of each of the time-domain symbols as the inverse Fourier selection result, then performing a predefined processing operation between a plurality of the time-domain symbols, and resolving the signalling information based on an obtained inter-symbol processing result.
 79. The preamble symbol receiving method of claim 72, characterized in that the predefined mathematical calculation contains: conjugate multiplication or division calculation.
 80. The preamble symbol receiving method of claim 72, characterized in that the step of performing a predefined processing operation between a plurality of the time-domain symbols and resolving the signalling information based on an obtained inter-symbol processing result comprises: multiplying or conjugate multiplying a later time-domain symbol which have been cyclically shifted and a former time-domain symbol, and accumulating to obtain an accumulated value, finding out a shift corresponding to a maximum accumulated value in all the predefined frequency offset values or cyclic shift values, and deriving the signalling information from the shift value.
 81. The preamble symbol receiving method of claim 71, characterized in that the method comprises: the step of determining the position of the preamble symbol and parsing signalling information carried by the preamble symbol comprises: extending the set of known frequency-domain signalling of each time-domain symbol to be an extended set of known frequency-domain signalling, performing Fourier transform on the time-domain main body signal of each of the time-domain symbol to extract valid subcarriers; performing predefined mathematical calculation using each of the valid subcarriers and the known subcarrier corresponding to each known frequency-domain sequence in the extended set of known frequency-domain signalling and the channel estimation value, and then accumulating the calculation values on all the valid subcarriers; and selecting an accumulated value from a plurality of accumulated values according to a second predefined selection rule, using a known frequency-domain sequence of the extended set of known frequency-domain signalling corresponding to the accumulated value to infer the signalling which is transmitted by utilizing the frequency-domain modulation frequency offset value, i.e. the time-domain cyclic shift, and inferring a corresponding known frequency-domain sequence in the original set of known frequency-domain signalling before extension, so as to resolve signalling information transmitted by a different frequency-domain sequence.
 82. The preamble symbol receiving method of claim 81, characterized in that the second predefined selection rule contains performing selection according to the maximum absolute value or performing selection according to the maximum of real part.
 83. The preamble symbol receiving method of claim 81, characterized in that the set of known frequency-domain signalling refers to all possible frequency-domain sequences of the time-domain main body signal corresponding to each time-domain symbol that are used for filling the frequency-domain subcarriers while phase modulation is not performed.
 84. The preamble symbol receiving method of claim 81, characterized in that the extended set of known frequency-domain signalling is obtained in the following way: modulating the subcarrier phase of each known frequency-domain sequence of the set of known frequency-domain signalling correspondingly using all possible frequency offset values, wherein all the possible S modulation frequency offset values will generate S frequency offset modulated known sequences.
 85. The preamble symbol receiving method of claim 81, characterized in that when there is only one known sequence within the non-extended set of known frequency-domain signalling of the symbol, namely, the signalling information is transmitted only by a frequency-domain modulation frequency offset s, i.e., the time-domain cyclic shift value, the extended set of known frequency-domain signalling contains altogether S known frequency-domain sequences, and the modulation frequency offset value can be inferred by utilizing the known frequency-domain sequences of the extended set of known frequency-domain signalling corresponding to the modulation frequency offset s, thus obtaining the signalling information transmitted by the frequency-domain modulation frequency offset, i.e. the time-domain cyclic shift.
 86. The preamble symbol receiving method of claim 81, characterized in that the predefined mathematical calculation contains: conjugate multiplication or division calculation.
 87. The preamble symbol receiving method of claim 71, characterized in that the method comprises: the step of determining the position of the preamble symbol and parsing signalling information carried by the preamble symbol comprises: performing Fourier transform on the time-domain main body signal of each of the time-domain symbol to extract valid subcarriers; performing predefined mathematical calculation using each of the valid subcarriers and a known subcarrier corresponding to each known frequency-domain sequence in a set of known frequency-domain signalling of the time-domain symbol and a channel estimation value, and then performing inverse Fourier transform, and obtaining a corresponding inverse Fourier result for each of the known frequency-domain sequence; and each of the time-domain symbol, based on an inverse Fourier selection result selected from one or more of the inverse Fourier results according to a first predefined selection rule, performing a predefined processing operation between a plurality of the time-domain symbols, and resolving the signalling information based on an obtained inter-symbol processing result.
 88. The preamble symbol receiving method of claim 87, characterized in that the predefined sending rule contains: after processing a frequency-domain main body sequence corresponding to a time-domain main body signal in each transmitted time-domain signal to obtain pre-generated subcarriers, performing phase modulation on each valid subcarrier using a predefined frequency offset value S in the frequency domain or performing cyclic shift in the time domain after inverse Fourier transform.
 89. The preamble symbol receiving method of claim 87, characterized in that the method further comprises: calculating the absolute value or square of the absolute value of the inverse Fourier selection result, and then selecting the inverse Fourier selection result according to the first predefined selection rule.
 90. The preamble symbol receiving method of claim 87, characterized in that the first predefined selection rule contains performing selection according to the maximum peak value and/or performing selection according to the peak-to-average ratio.
 91. The preamble symbol receiving method of claim 87, characterized in that the method further comprises: a noise filtering processing step comprising: noise filtering processing can be performed on the inverse Fourier result of each time-domain symbol, with large values being reserved and all smaller values being set to zero.
 92. The preamble symbol receiving method of claim 87, characterized in that the parsed signalling information contains: signalling transmitted using different frequency-domain sequences and/or signalling transmitted using frequency-domain modulation frequency offset, i.e. a time-domain cyclic shift value.
 93. The preamble symbol receiving method of claim 87, characterized in that the set of known frequency-domain signalling refers to all possible sequences of the time-domain main body signal corresponding to each time-domain symbol that are used for filling the frequency-domain subcarriers before performing phase modulation on of the frequency-domain subcarriers.
 94. The preamble symbol receiving method of claim 87, characterized in that if there is only one known sequence within a set of known frequency-domain sequences of the time-domain symbols, the first predefined selection rule is: directly selecting the unique inverse Fourier result of each of the time-domain symbols as the inverse Fourier selection result, then performing a predefined processing operation between a plurality of the time-domain symbols, and resolving the signalling information based on an obtained inter-symbol processing result.
 95. The preamble symbol receiving method of claim 87, characterized in that the predefined mathematical calculation contains: conjugate multiplication or division calculation.
 96. The preamble symbol receiving method of claim 87, characterized in that the step of performing a predefined processing operation on a plurality of the time-domain symbols, and resolving the signalling information based on an obtained inter-symbol processing result comprises: multiplying or conjugate multiplying a later time-domain symbol which have been cyclically shifted and a former time-domain symbol, and accumulating to obtain an accumulated value, finding out a shift value corresponding to a maximum accumulated value in all the predefined frequency offset values or cyclic shift values, and deriving the signalling information from the shift value.
 97. A preamble symbol receiving device, characterized by comprising: a receiving and processing unit for processing a received signal; a judgement unit for judging whether the processed signal obtained contains the preamble symbol desired to be received; and a positioning and parsing unit for, if a judgement result is yes, determining the position of the preamble symbol and resolving signalling information carried by the preamble symbol, wherein the preamble symbol received by the receiving and processing unit comprises at least one time-domain symbol generated by a sending end using a free combination of any number of first three-segment structures and/or second three-segment structures according to a predefined generation rule, the first three-segment structure containing: a time-domain main body signal, a prefix generated based on the entirety or a portion of the time-domain main body signal, and a postfix generated based on the entirety or a portion of a partial time-domain main body signal, and the second three-segment structure containing: the time-domain main body signal, a prefix generated based on the entirety or a portion of the time-domain main body signal, and a hyper prefix generated based on the entirety or a portion of the partial time-domain main body signal.
 98. A preamble symbol receiving device, characterized by comprising: a receiving and processing unit for processing a received signal; a judgement unit for judging whether the processed signal obtained contains the preamble symbol desired to be received; and a positioning and parsing unit for, if a judgement result is yes, determining the position of the preamble symbol and resolving signalling information carried by the preamble symbol, wherein the preamble symbol received by the receiving and processing unit is obtained by processing a frequency-domain symbol, and the generation step of the frequency-domain symbol comprises: arranging a fixed sequence and a signalling sequence, which are generated respectively, in a predefined arrangement rule, and filling valid subcarriers with the arranged fixed sequence and signalling sequence.
 99. A preamble symbol receiving device, characterized by comprising: a receiving unit for processing a received signal; a judgement unit for judging whether the processed signal obtained contains the preamble symbol desired to be received; and a positioning and parsing unit for, if a judgement result is yes, determining the position of the preamble symbol and resolving signalling information carried by the preamble symbol, wherein the preamble symbol received by the receiving unit is obtained by performing inverse Fourier transform on the frequency-domain subcarrier, the frequency-domain subcarrier being generated based on the frequency-domain main body sequence, the steps of generating the frequency-domain subcarrier contains: a predefined sequence generation rule for generating the frequency-domain main body sequence, and/or a predefined processing rule for generating the frequency-domain subcarrier by utilizing the frequency-domain main body sequence; the predefined sequence generation rule contains either one of or a combination of two of the following: generating a sequence based on different sequence generation formulas; and/or preforming cyclic shift on a sequence generated based on the same sequence generation formula. the predefined processing rule contains: according to the frequency offset value, performing phase modulation on a pre-generated subcarrier which is obtained by processing the frequency-domain main body sequence. 